ANALOG DEVICES AD8629

Zero-Drift, Single-Supply, Rail-to-Rail Input/Output Operational Amplifier AD8628/AD8629/AD8630 FEATURES PIN CONFIGURATIONS Lowest auto-zero amplifier noise OUT 1 5 V+ AD8628 Low offset voltage: 1 μV TOP VIEW V– 2 Input offset drift: 0.002 μV/°C (Not to Scale) Rail-to-rail input and output swing +IN 3 4 –IN 5 V single-supply operation Figure 1. 5-Lead TSOT (UJ-5) and 5-Lead SOT-23 (RJ-5) High gain, CMRR, and PSRR: 130 dB Very low input bias current: 100 pA maximum Low supply current: 1.0 mA NC 1 8 NC Overload recovery time: 50 μs AD8628 –IN 2 7 V+ No external components required +IN 3 6 OUT TOP VIEW (Not to Scale) Qualified for automotive applications V– 4 5 NC NC = NO CONNECT Figure 2. 8-Lead SOIC_N (R-8) APPLICATIONS Automotive sensors Pressure and position sensors OUT A 1 8 V+ Strain gage amplifiers AD8629 –IN A 2 7 OUT B TOP VIEW Medical instrumentation +IN A 3 6 –IN B (Not to Scale) Thermocouple amplifiers V– 4 5 +IN B Precision current sensing Figure 3. 8-Lead SOIC_N (R-8) and 8-Lead MSOP (RM-8) Photodiode amplifiers 1 14 OUT D GENERAL DESCRIPTION OUT A –IN A 2 13 –IN D This amplifier has ultralow offset, drift, and bias current. +IN A 3 12 +IN D AD8630 The AD8628/AD8629/AD8630 are wide bandwidth auto-zero V+ 4 TOP VIEW 11 V– (Not to Scale) amplifiers featuring rail-to-rail input and output swing and low +IN B 5 10 +IN C –IN B 6 9 –IN C noise. Operation is fully specified from 2.7 V to 5 V single supply OUT B 7 8 OUT C (±1.35 V to ±2.5 V dual supply). Figure 4. 14-Lead SOIC_N (R-14) and 14-Lead TSSOP (RU-14) The AD8628/AD8629/AD8630 provide benefits previously found only in expensive auto-zeroing or chopper-stabilized amplifiers. Using Analog Devices, Inc., topology, these zero- The AD8628/AD8629/AD8630 are specified for the extended drift amplifiers combine low cost with high accuracy and low industrial temperature range (−40°C to +125°C). The AD8628 noise. No external capacitor is required. In addition, the AD8628/ is available in tiny 5-lead TSOT, 5-lead SOT-23, and 8-lead AD8629/AD8630 greatly reduce the digital switching noise narrow SOIC plastic packages. The AD8629 is available in the found in most chopper-stabilized amplifiers. standard 8-lead narrow SOIC and MSOP plastic packages. The With an offset voltage of only 1 μV, drift of less than 0.005 μV/°C, AD8630 quad amplifier is available in 14-lead narrow SOIC and and noise of only 0.5 μV p-p (0 Hz to 10 Hz), the AD8628/ 14-lead TSSOP plastic packages. See the Ordering Guide for AD8629/AD8630 are suited for applications where error automotive grades. sources cannot be tolerated. Position and pressure sensors, medical equipment, and strain gage amplifiers benefit greatly from nearly zero drift over their operating temperature range. Many systems can take advantage of the rail-to-rail input and output swings provided by the AD8628/AD8629/AD8630 to reduce input biasing complexity and maximize SNR. Rev. I Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. rights of third parties that may result from its use. Specifications subject to change without notice. No Tel: 781.329.4700 www.analog.com license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Fax: 781.461.3113 ©2002–2011 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. 02735-002 02735-001 02735-066 02735-063 AD8628/AD8629/AD8630 TABLE OF CONTENTS Features .............................................................................................. 1  1/f Noise....................................................................................... 14  Applications....................................................................................... 1  Peak-to-Peak Noise .................................................................... 15  General Description ......................................................................... 1  Noise Behavior with First-Order, Low-Pass Filter................. 15  Pin Configurations ........................................................................... 1  Total Integrated Input-Referred Noise for First-Order Filter15  Revision History ............................................................................... 2  Input Overvoltage Protection ................................................... 16  Specifications..................................................................................... 3  Output Phase Reversal............................................................... 16  Electrical Characteristics—V = 5.0 V....................................... 3  Overload Recovery Time .......................................................... 16  S Electrical Characteristics—V = 2.7 V....................................... 4  Infrared Sensors.......................................................................... 17  S Absolute Maximum Ratings............................................................ 5  Precision Current Shunt Sensor ............................................... 18  Thermal Characteristics .............................................................. 5  Output Amplifier for High Precision DACs........................... 18  ESD Caution.................................................................................. 5  Outline Dimensions....................................................................... 19  Typical Performance Characteristics ............................................. 6  Ordering Guide .......................................................................... 21  Functional Description .................................................................. 14  REVISION HISTORY 4/11—Rev. H to Rev. I Added Figure 5 and Figure 6............................................................1 Updated Outline Dimensions ....................................................... 19 Changes to Caption in Figure 8 and Figure 9................................7 Changes to Ordering Guide .......................................................... 21 Changes to Caption in Figure 14.....................................................8 Changes to Figure 17.........................................................................8 4/10—Rev. G to Rev. H Changes to Figure 23 and Figure 24................................................9 Change to Features List.................................................................... 1 Changes to Figure 25 and Figure 26............................................. 10 Change to General Description Section ........................................ 1 Changes to Figure 31...................................................................... 11 Changes to Table 3............................................................................ 5 Changes to Figure 40, Figure 41, Figure 42................................. 12 Updated Outline Dimensions Section......................................... 19 Changes to Figure 43 and Figure 44............................................. 13 Changes to Ordering Guide .......................................................... 21 Changes to Figure 51...................................................................... 15 Updated Outline Dimensions....................................................... 20 6/08—Rev. F to Rev. G Changes to Ordering Guide .......................................................... 20 Changes to Features Section............................................................ 1 Changes to Table 5 and Figure 42 Caption ................................. 12 10/04—Rev. B to Rev. C Changes to 1/f Noise Section and Figure 49 ............................... 14 Updated Formatting...........................................................Universal Changes to Figure 51 Caption and Figure 55 ............................. 15 Added AD8629 ...................................................................Universal Changes to Figure 57 Caption and Figure 58 Caption .............. 16 Added SOIC and MSOP Pin Configurations ................................1 Changes to Figure 60 Caption and Figure 61 Caption .............. 17 Added Figure 48 ............................................................................. 13 Changes to Figure 64...................................................................... 18 Changes to Figure 62...................................................................... 17 Added MSOP Package ................................................................... 19 2/08—Rev. E to Rev. F Changes to Ordering Guide .......................................................... 22 Renamed TSOT-23 to TSOT ............................................Universal Deleted Figure 4 and Figure 6......................................................... 1 10/03—Rev. A to Rev. B Changes to Figure 3 and Figure 4 Captions .................................. 1 Changes to General Description .....................................................1 Changes to Table 1............................................................................ 3 Changes to Absolute Maximum Ratings........................................4 Changes to Table 2............................................................................ 4 Changes to Ordering Guide .............................................................4 Changes to Table 4............................................................................ 5 Added TSOT-23 Package .............................................................. 15 Updated Outline Dimensions ....................................................... 19 Changes to Ordering Guide .......................................................... 20 6/03—Rev. 0 to Rev. A Changes to Specifications.................................................................3 5/05—Rev. D to Rev. E Changes to Ordering Guide .............................................................4 Changes to Ordering Guide .......................................................... 22 Change to Functional Description............................................... 10 Updated Outline Dimensions....................................................... 15 1/05—Rev. C to Rev. D Added AD8630 ...................................................................Universal 10/02—Revision 0: Initial Version Rev. I | Page 2 of 24 AD8628/AD8629/AD8630 SPECIFICATIONS ELECTRICAL CHARACTERISTICS—V = 5.0 V S V = 5.0 V, V = 2.5 V, T = 25°C, unless otherwise noted. S CM A Table 1. Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage VOS 1 5 μV −40°C ≤ T ≤ +125°C 10 μV A Input Bias Current I B AD8628/AD8629 30 100 pA AD8630 100 300 pA −40°C ≤ TA ≤ +125°C 1.5 nA Input Offset Current I 50 200 pA OS −40°C ≤ T ≤ +125°C 250 pA A Input Voltage Range 0 5 V Common-Mode Rejection Ratio CMRR VCM = 0 V to 5 V 120 140 dB −40°C ≤ TA ≤ +125°C 115 130 dB Large Signal Voltage Gain AVO RL = 10 kΩ, VO = 0.3 V to 4.7 V 125 145 dB −40°C ≤ T ≤ +125°C 120 135 dB A Offset Voltage Drift ∆V/∆T −40°C ≤ T ≤ +125°C 0.002 0.02 μV/°C OS A OUTPUT CHARACTERISTICS Output Voltage High V R = 100 kΩ to ground 4.99 4.996 V OH L −40°C ≤ T ≤ +125°C 4.99 4.995 V A RL = 10 kΩ to ground 4.95 4.98 V −40°C ≤ TA ≤ +125°C 4.95 4.97 V Output Voltage Low VOL RL = 100 kΩ to V+ 1 5 mV −40°C ≤ T ≤ +125°C 2 5 mV A R = 10 kΩ to V+ 10 20 mV L −40°C ≤ T ≤ +125°C 15 20 mV A Short-Circuit Limit ISC ±25 ±50 mA −40°C ≤ TA ≤ +125°C ±40 mA Output Current IO ±30 mA −40°C ≤ T ≤ +125°C ±15 mA A POWER SUPPLY Power Supply Rejection Ratio PSRR V = 2.7 V to 5.5 V, −40°C ≤ T ≤ +125°C 115 130 dB S A Supply Current per Amplifier I V = V /2 0.85 1.1 mA SY O S −40°C ≤ T ≤ +125°C 1.0 1.2 mA A INPUT CAPACITANCE C IN Differential 1.5 pF Common Mode 8.0 pF DYNAMIC PERFORMANCE Slew Rate SR R = 10 kΩ 1.0 V/μs L Overload Recovery Time 0.05 ms Gain Bandwidth Product GBP 2.5 MHz NOISE PERFORMANCE Voltage Noise e p-p 0.1 Hz to 10 Hz 0.5 μV p-p n 0.1 Hz to 1.0 Hz 0.16 μV p-p Voltage Noise Density en f = 1 kHz 22 nV/√Hz Current Noise Density i f = 10 Hz 5 fA/√Hz n Rev. I | Page 3 of 24 AD8628/AD8629/AD8630 ELECTRICAL CHARACTERISTICS—V = 2.7 V S VS = 2.7 V, VCM = 1.35 V, VO = 1.4 V, TA = 25°C, unless otherwise noted. Table 2. Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage VOS 1 5 μV −40°C ≤ TA ≤ +125°C 10 μV Input Bias Current IB AD8628/AD8629 30 100 pA AD8630 100 300 pA −40°C ≤ TA ≤ +125°C 1.0 1.5 nA Input Offset Current IOS 50 200 pA −40°C ≤ TA ≤ +125°C 250 pA Input Voltage Range 0 2.7 V Common-Mode Rejection Ratio CMRR V = 0 V to 2.7 V 115 130 dB CM −40°C ≤ T ≤ +125°C 110 120 dB A Large Signal Voltage Gain AVO RL = 10 kΩ, VO = 0.3 V to 2.4 V 110 140 dB −40°C ≤ TA ≤ +125°C 105 130 dB Offset Voltage Drift ∆VOS/∆T −40°C ≤ TA ≤ +125°C 0.002 0.02 μV/°C OUTPUT CHARACTERISTICS Output Voltage High VOH RL = 100 kΩ to ground 2.68 2.695 V −40°C ≤ T ≤ +125°C 2.68 2.695 V A R = 10 kΩ to ground 2.67 2.68 V L −40°C ≤ T ≤ +125°C 2.67 2.675 V A Output Voltage Low VOL RL = 100 kΩ to V+ 1 5 mV −40°C ≤ TA ≤ +125°C 2 5 mV RL = 10 kΩ to V+ 10 20 mV −40°C ≤ T ≤ +125°C 15 20 mV A Short-Circuit Limit I ±10 ±15 mA SC −40°C ≤ T ≤ +125°C ±10 mA A Output Current IO ±10 mA −40°C ≤ TA ≤ +125°C ±5 mA POWER SUPPLY Power Supply Rejection Ratio PSRR VS = 2.7 V to 5.5 V, −40°C ≤ TA ≤ +125°C 115 130 dB Supply Current per Amplifier ISY VO = VS/2 0.75 1.0 mA −40°C ≤ T ≤ +125°C 0.9 1.2 mA A INPUT CAPACITANCE CIN Differential 1.5 pF Common Mode 8.0 pF DYNAMIC PERFORMANCE Slew Rate SR RL = 10 kΩ 1 V/μs Overload Recovery Time 0.05 ms Gain Bandwidth Product GBP 2 MHz NOISE PERFORMANCE Voltage Noise e p-p 0.1 Hz to 10 Hz 0.5 μV p-p n Voltage Noise Density e f = 1 kHz 22 nV/√Hz n Current Noise Density i f = 10 Hz 5 fA/√Hz n Rev. I | Page 4 of 24 AD8628/AD8629/AD8630 ABSOLUTE MAXIMUM RATINGS Table 3. Parameter Rating THERMAL CHARACTERISTICS Supply Voltage 6 V θ is specified for worst-case conditions, that is, θ is specified JA JA Input Voltage GND – 0.3 V to V + 0.3 V S for the device soldered in a circuit board for surface-mount 1 Differential Input Voltage ±5.0 V packages. This was measured using a standard two-layer board. Output Short-Circuit Duration to GND Indefinite Table 4. Storage Temperature Range −65°C to +150°C Operating Temperature Range −40°C to +125°C Package Type θJA θJC Unit Junction Temperature Range −65°C to +150°C 5-Lead TSOT (UJ-5) 207 61 °C/W Lead Temperature (Soldering, 60 sec) 300°C 5-Lead SOT-23 (RJ-5) 230 146 °C/W ESD AD8628 8-Lead SOIC_N (R-8) 158 43 °C/W HBM 8-Lead SOIC ±7000V 8-Lead MSOP (RM-8) 190 44 °C/W FICDM 8-Lead SOIC ±1500V 14-Lead SOIC_N (R-14) 105 43 °C/W FICDM 5-Lead TSOT ±1000V 14-Lead TSSOP (RU-14) 148 23 °C/W MM 8-Lead SOIC ±200V ESD AD8629 ESD CAUTION HBM 8-Lead SOIC ±4000V FICDM 8-Lead SOIC ±1000V ESD AD8630 HBM 14-Lead SOIC ±5000V FICDM 14-Lead SOIC ±1500V FICDM 14-Lead TSSOP ±1500V MM 14-Lead SOIC ±200V 1 Differential input voltage is limited to ±5 V or the supply voltage, whichever is less. Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. I | Page 5 of 24 AD8628/AD8629/AD8630 TYPICAL PERFORMANCE CHARACTERISTICS 180 100 V = 2.7V V = 5V S S 90 160 T = 25°C V = 2.5V A CM T = 25°C A 80 140 70 120 60 100 50 80 40 60 30 40 20 20 10 0 0 –2.5 –1.5 –0.5 0.5 1.5 2.5 –2.5 –1.5 –0.5 0.5 1.5 2.5 INPUT OFFSET VOLTAGE (µV) INPUT OFFSET VOLTAGE (µV) Figure 5. Input Offset Voltage Distribution Figure 8. Input Offset Voltage Distribution 60 7 V = 5V S V = 5V S +85°C T = –40°C TO +125°C 6 A 50 5 40 4 30 3 20 +25°C 2 10 1 –40°C 0 0 012 3 4 5 6 0 2 4 68 10 INPUT COMMON-MODE VOLTAGE (V) TCVOS (nV/°C) Figure 6. AD8628 Input Bias Current vs. Input Common-Mode Voltage Figure 9. Input Offset Voltage Drift 1500 1k V = 5V S V = 5V S 150°C T = 25°C A 1000 100 125°C 500 10 SOURCE 0 SINK 1 –500 0.1 –1000 –1500 0.01 012 3 4 5 6 0.0001 0.001 0.01 0.1 1 10 INPUT COMMON-MODE VOLTAGE (V) LOAD CURRENT (mA) Figure 7. AD8628 Input Bias Current vs. Input Common-Mode Voltage Figure 10. Output Voltage to Supply Rail vs. Load Current Rev. I | Page 6 of 24 NUMBER OF AMPLIFIERS INPUT BIAS CURRENT (pA) INPUT BIAS CURRENT (pA) 02735-004 02735-005 02735-003 NUMBER OF AMPLIFIERS OUTPUT VOLTAGE (mV) NUMBER OF AMPLIFIERS 02735-008 02735-007 02735-006 AD8628/AD8629/AD8630 1k 1000 T = 25°C V = 2.7V A S 100 800 10 600 SOURCE SINK 1 400 0.1 200 0.01 0 0.0001 0.001 0.01 0.1 1 10 01 236 4 5 LOAD CURRENT (mA) SUPPLY VOLTAGE (V) Figure 11. Output Voltage to Supply Rail vs. Load Current Figure 14. Supply Current vs. Supply Voltage 1500 V = 2.7V S V = 5V S 60 C = 20pF L V = 2.5V CM R = ∞ L T = –40°C TO +150°C A Ф = 45° 1150 M GAIN 40 0 45 900 PHASE 20 90 135 450 0 180 225 100 –20 0 10k 100k 1M 10M –50 –25 0 25 50 75 100 125 150 175 FREQUENCY (Hz) TEMPERATURE (°C) Figure 12. AD8628 Input Bias Current vs. Temperature Figure 15. Open-Loop Gain and Phase vs. Frequency 1250 70 T = 25°C V = 5V A S 60 C = 20pF L 5V R = ∞ L 1000 50 Φ = 52.1° M GAIN 40 0 2.7V 750 30 45 PHASE 20 90 500 10 135 0 180 250 –10 225 –20 0 –30 –50 0 50 100 150 200 10k 100k 1M 10M TEMPERATURE (°C) FREQUENCY (Hz) Figure 16. Open-Loop Gain and Phase vs. Frequency Figure 13. Supply Current vs. Temperature Rev. I | Page 7 of 24 SUPPLY CURRENT (µA) INPUT BIAS CURRENT (pA) OUTPUT VOLTAGE (mV) 02735-009 02735-011 02735-010 OPEN-LOOP GAIN (dB) OPEN-LOOP GAIN (dB) SUPPLY CURRENT (µA) 02735-012 PHASE SHIFT (Degrees) PHASE SHIFT (Degrees) 02735-014 02735-013 AD8628/AD8629/AD8630 70 300 V = 5V S V = 2.7V S 60 270 C = 20pF L R = 2kΩ L 50 240 A = 100 V 40 210 30 180 A = 10 V 20 150 10 120 A = 1 V 0 90 A = 10 –10 60 V A = 100 V –20 30 A = 1 V –30 0 1k 10k 100k 1M 10M 100 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) FREQUENCY (Hz) Figure 17. Closed-Loop Gain vs. Frequency Figure 20. Output Impedance vs. Frequency 70 V = 5V S 60 C = 20pF L R = 2kΩ L 50 A = 100 V 40 V = ±1.35V S 30 C = 300pF L A = 10 V R = ∞ L 0V 20 A = 1 V 10 A = 1 V 0 –10 –20 –30 1k 10k 100k 1M 10M TIME (4µs/DIV) FREQUENCY (Hz) Figure 18. Closed-Loop Gain vs. Frequency Figure 21. Large Signal Transient Response 300 V = 2.7V S 270 240 210 V = ±2.5V S C = 300pF 180 L R = ∞ L 0V 150 A = 1 V 120 90 A = 10 60 V A = 100 V 30 A = 1 V 0 100 1k 10k 100k 1M 10M 100M TIME (5µs/DIV) FREQUENCY (Hz) Figure 22. Large Signal Transient Response Figure 19. Output Impedance vs. Frequency Rev. I | Page 8 of 24 OUTPUT IMPEDANCE (Ω) CLOSED-LOOP GAIN (dB) CLOSED-LOOP GAIN (dB) 02735-016 02735-015 02735-017 OUTPUT IMPEDANCE (Ω) VOLTAGE (1V/DIV) VOLTAGE (500mV/DIV) 02735-020 02735-019 02735-018 AD8628/AD8629/AD8630 80 V = ±2.5V V = ±1.35V S S R = 2kΩ C = 50pF L L 70 T = 25°C R = ∞ L A A = 1 V 60 50 0V 40 30 OS– 20 OS+ 10 0 110 100 1k TIME (4µs/DIV) CAPACITIVE LOAD (pF) Figure 23. Small Signal Transient Response Figure 26. Small Signal Overshoot vs. Load Capacitance V = ±2.5V S V = ±2.5V S A = –50 V C = 50pF L V IN R = 10kΩ R = ∞ L L C = 0pF A = 1 L V CH1 = 50mV/DIV CH2 = 1V/DIV 0V 0V 0V V OUT TIME (4µs/DIV) TIME (2µs/DIV) Figure 24. Small Signal Transient Response Figure 27. Positive Overvoltage Recovery 100 V = ±1.35V S R = 2kΩ 90 L 0V T = 25°C A V = ±2.5V S 80 A = –50 V R = 10kΩ L 70 V C = 0pF IN L CH1 = 50mV/DIV 60 CH2 = 1V/DIV OS– 50 V OUT 40 OS+ 30 20 0V 10 0 110 100 1k TIME (10µs/DIV) CAPACITIVE LOAD (pF) Figure 25. Small Signal Overshoot vs. Load Capacitance Figure 28. Negative Overvoltage Recovery Rev. I | Page 9 of 24 OVERSHOOT (%) VOLTAGE (50mV/DIV) VOLTAGE (50mV/DIV) 02735-022 02735-021 02735-023 OVERSHOOT (%) VOLTAGE (V) VOLTAGE (V) 02735-025 02735-026 02735-024 AD8628/AD8629/AD8630 140 V = ±2.5V S V = ±1.35V S V = 1kHz @ ±3V p-p 120 IN C = 0pF L R = 10kΩ L 100 A = 1 V 80 60 +PSRR 0V 40 20 –PSRR 0 –20 –40 –60 100 1k 10k 100k 1M 10M TIME (200µs/DIV) FREQUENCY (Hz) Figure 29. No Phase Reversal Figure 32. PSRR vs. Frequency 140 140 V = ±2.5V V = 2.7V S S 120 120 100 100 80 80 60 60 +PSRR 40 40 –PSRR 20 20 0 0 –20 –20 –40 –40 –60 –60 100 1k 10k 100k 1M 10M 100 1k 10k 100k 1M 10M FREQUENCY (Hz) FREQUENCY (Hz) Figure 30. CMRR vs. Frequency Figure 33. PSRR vs. Frequency 140 3.0 V = 5V V = 2.7V S S R = 10kΩ 120 L T = 25°C A 2.5 A = 1 100 V 80 2.0 60 40 1.5 20 1.0 0 –20 0.5 –40 –60 0 100 1k 10k 100k 1M 10M 100 1k 10k 100k 1M FREQUENCY (Hz) FREQUENCY (Hz) Figure 31. CMRR vs. Frequency Figure 34. Maximum Output Swing vs. Frequency Rev. I | Page 10 of 24 CMRR (dB) CMRR (dB) VOLTAGE (1V/DIV) 02735-027 02735-029 02735-028 PSRR (dB) PSRR (dB) OUTPUT SWING (V p-p) 02735-032 02735-031 02735-030 AD8628/AD8629/AD8630 5.5 120 V = 5V S V = 2.7V S 5.0 R = 10kΩ L NOISE AT 1kHz = 21.3nV 105 T = 25°C A 4.5 A = 1 V 90 4.0 3.5 75 3.0 60 2.5 2.0 45 1.5 30 1.0 15 0.5 0 0 100 1k 10k 100k 1M 0 0.5 1.0 1.5 2.0 2.5 FREQUENCY (Hz) FREQUENCY (kHz) Figure 35. Maximum Output Swing vs. Frequency Figure 38. Voltage Noise Density at 2.7 V from 0 Hz to 2.5 kHz 0.60 120 V = 2.7V S V = 2.7V S NOISE AT 10kHz = 42.4nV 0.45 105 0.30 90 0.15 75 0 60 –0.15 45 –0.30 30 –0.45 15 –0.60 0 0 1 2 3 4 5678 9 10 0 5 10 15 20 25 TIME (µs) FREQUENCY (kHz) Figure 36. 0.1 Hz to 10 Hz Noise Figure 39. Voltage Noise Density at 2.7 V from 0 Hz to 25 kHz 0.60 120 V = 5V S V = 5V S NOISE AT 1kHz = 22.1nV 0.45 105 0.30 90 0.15 75 0 60 –0.15 45 –0.30 30 –0.45 15 –0.60 0 0 1 2 3 4 5678 9 10 0 0.5 1.0 1.5 2.0 2.5 TIME (µs) FREQUENCY (kHz) Figure 37. 0.1 Hz to 10 Hz Noise Figure 40. Voltage Noise Density at 5 V from 0 Hz to 2.5 kHz Rev. I | Page 11 of 24 VOLTAGE (µV) VOLTAGE (µV) OUTPUT SWING (V p-p) 02735-035 02735-034 02735-033 VOLTAGE NOISE DENSITY (nV/√Hz) VOLTAGE NOISE DENSITY (nV/√Hz) VOLTAGE NOISE DENSITY (nV/√Hz) 02735-038 02735-037 02735-036 AD8628/AD8629/AD8630 120 150 V = 2.7V S V = 5V S T = –40°C TO +150°C A NOISE AT 10kHz = 36.4nV 105 100 90 75 50 60 I – SC 0 45 I + SC 30 –50 15 0 –100 0 5 10 15 20 25 –50 –25 0 25 50 75 100 125 150 175 FREQUENCY (kHz) TEMPERATURE (°C) Figure 41. Voltage Noise Density at 5 V from 0 Hz to 25 kHz Figure 44. Output Short-Circuit Current vs. Temperature 120 150 V = 5V S V = 5V S T = –40°C TO +150°C A 105 100 90 I – SC 75 50 60 0 45 30 –50 15 I + SC 0 –100 05 10 –50 –25 0 25 50 75 100 125 150 175 FREQUENCY (kHz) TEMPERATURE (°C) Figure 42. Voltage Noise Density at 5 V from 0 Hz to 10 kHz Figure 45. Output Short-Circuit Current vs. Temperature 150 1k V = 5V S 140 V – V @ 1kΩ CC OH 130 100 V = 2.7V TO 5V S 120 T = –40°C TO +125°C A V – V @ 1kΩ OL EE 110 V – V @ 10kΩ CC OH 100 10 V – V @ 10kΩ OL EE 90 V – V @ 100kΩ CC OH 80 1 V – V @ 100kΩ OL EE 70 60 50 0.1 –50 –25 0 25 50 75 100 125 –50 –25 0 25 50 75 100 125 150 175 TEMPERATURE (°C) TEMPERATURE (°C) Figure 43. Power Supply Rejection vs. Temperature Figure 46. Output-to-Rail Voltage vs. Temperature Rev. I | Page 12 of 24 POWER SUPPLY REJECTION (dB) VOLTAGE NOISE DENSITY (nV/√Hz) VOLTAGE NOISE DENSITY (nV/√Hz) 02735-040 02735-039 02735-041 OUTPUT-TO-RAIL VOLTAGE (mV) OUTPUT SHORT-CIRCUIT CURRENT (mA) OUTPUT SHORT-CIRCUIT CURRENT (mA) 02735-042 02735-044 02735-043 AD8628/AD8629/AD8630 1k 140 V = 2.7V S V = ±2.5V S 120 V – V @ 1kΩ CC OH 100 100 V – V @ 1kΩ OL EE 80 V – V @ 10kΩ CC OH 10 R1 V – V @ 10kΩ OL EE 60 10kΩ +2.5V R2 V – V @ 100kΩ CC OH 100Ω V+ V– 40 + V IN 1 AB V – V @ 100kΩ 28mV p-p OL EE V OUT – V– V+ 20 –2.5V 0.1 0 –50 –25 0 25 50 75 100 125 150 175 1k 10k 100k 1M 10M TEMPERATURE (°C) FREQUENCY (Hz) Figure 47. Output-to-Rail Voltage vs. Temperature Figure 48. AD8629/AD8630 Channel Separation vs. Frequency Rev. I | Page 13 of 24 OUTPUT-TO-RAIL VOLTAGE (mV) 02735-045 CHANNEL SEPARATION (dB) 02735-062 AD8628/AD8629/AD8630 FUNCTIONAL DESCRIPTION The AD8628/AD8629/AD8630 are single-supply, ultrahigh 1/f NOISE precision rail-to-rail input and output operational amplifiers. 1/f noise, also known as pink noise, is a major contributor to The typical offset voltage of less than 1 μV allows these amplifiers errors in dc-coupled measurements. This 1/f noise error term to be easily configured for high gains without risk of excessive can be in the range of several μV or more, and, when amplified output voltage errors. The extremely small temperature drift with the closed-loop gain of the circuit, can show up as a large of 2 nV/°C ensures a minimum offset voltage error over their output offset. For example, when an amplifier with a 5 μV p-p entire temperature range of −40°C to +125°C, making these 1/f noise is configured for a gain of 1000, its output has 5 mV of amplifiers ideal for a variety of sensitive measurement applica- error due to the 1/f noise. However, the AD8628/AD8629/AD8630 tions in harsh operating environments. eliminate 1/f noise internally, thereby greatly reducing output errors. The AD8628/AD8629/AD8630 achieve a high degree of precision The internal elimination of 1/f noise is accomplished as follows. through a patented combination of auto-zeroing and chopping. 1/f noise appears as a slowly varying offset to the AD8628/AD8629/ This unique topology allows the AD8628/AD8629/AD8630 to AD8630 inputs. Auto-zeroing corrects any dc or low frequency maintain their low offset voltage over a wide temperature range offset. Therefore, the 1/f noise component is essentially removed, and over their operating lifetime. The AD8628/AD8629/AD8630 leaving the AD8628/AD8629/AD8630 free of 1/f noise. also optimize the noise and bandwidth over previous generations One advantage that the AD8628/AD8629/AD8630 bring to of auto-zero amplifiers, offering the lowest voltage noise of any system applications over competitive auto-zero amplifiers is their auto-zero amplifier by more than 50%. very low noise. The comparison shown in Figure 49 indicates Previous designs used either auto-zeroing or chopping to add an input-referred noise density of 19.4 nV/√Hz at 1 kHz for precision to the specifications of an amplifier. Auto-zeroing the AD8628, which is much better than the Competitor A results in low noise energy at the auto-zeroing frequency, at the and Competitor B. The noise is flat from dc to 1.5 kHz, slowly expense of higher low frequency noise due to aliasing of wideband increasing up to 20 kHz. The lower noise at low frequency is noise into the auto-zeroed frequency band. Chopping results in desirable where auto-zero amplifiers are widely used. lower low frequency noise at the expense of larger noise energy 120 at the chopping frequency. The AD8628/AD8629/AD8630 COMPETITOR A 105 family uses both auto-zeroing and chopping in a patented ping- (89.7nV/√Hz) pong arrangement to obtain lower low frequency noise together 90 with lower energy at the chopping and auto-zeroing frequencies, 75 maximizing the signal-to-noise ratio for the majority of applications without the need for additional filtering. The 60 relatively high clock frequency of 15 kHz simplifies filter COMPETITOR B 45 requirements for a wide, useful noise-free bandwidth. (31.1nV/√Hz) The AD8628 is among the few auto-zero amplifiers offered in 30 the 5-lead TSOT package. This provides a significant improvement 15 AD8628 over the ac parameters of the previous auto-zero amplifiers. The MK AT 1kHz FOR ALL 3 GRAPHS (19.4nV/√Hz) 0 AD8628/AD8629/AD8630 have low noise over a relatively wide 042861012 bandwidth (0 Hz to 10 kHz) and can be used where the highest FREQUENCY (kHz) dc precision is required. In systems with signal bandwidths of Figure 49. Noise Spectral Density of AD8628 vs. Competition from 5 kHz to 10 kHz, the AD8628/AD8629/AD8630 provide true 16-bit accuracy, making them the best choice for very high resolution systems. Rev. I | Page 14 of 24 VOLTAGE NOISE DENSITY (nV/√Hz) 02735-046 AD8628/AD8629/AD8630 50 PEAK-TO-PEAK NOISE 45 Because of the ping-pong action between auto-zeroing and 40 chopping, the peak-to-peak noise of the AD8628/AD8629/ 35 AD8630 is much lower than the competition. Figure 50 and Figure 51 show this comparison. 30 25 e p-p = 0.5µV n BW = 0.1Hz TO 10Hz 20 15 10 5 0 0 10 20 30 40 50 60 70 80 90 100 FREQUENCY (kHz) Figure 53. Simulation Transfer Function of the Test Circuit in Figure 52 50 45 40 TIME (1s/DIV) 35 Figure 50. AD8628 Peak-to-Peak Noise 30 25 20 e p-p = 2.3µV n BW = 0.1Hz TO 10Hz 15 10 5 0 0 10 20 30 40 50 60 70 80 90 100 FREQUENCY (kHz) Figure 54. Actual Transfer Function of the Test Circuit in Figure 52 The measured noise spectrum of the test circuit charted in Figure 54 shows that noise between 5 kHz and 45 kHz is successfully rolled off by the first-order filter. TOTAL INTEGRATED INPUT-REFERRED NOISE FOR TIME (1s/DIV) FIRST-ORDER FILTER Figure 51. Competitor A Peak-to-Peak Noise For a first-order filter, the total integrated noise from the NOISE BEHAVIOR WITH FIRST-ORDER, LOW-PASS AD8628 is lower than the noise of Competitor A. FILTER 10 The AD8628 was simulated as a low-pass filter (see Figure 53) and then configured as shown in Figure 52. The behavior of the COMPETITOR A AD8628 matches the simulated data. It was verified that noise is rolled off by first-order filtering. Figure 53 and Figure 54 show AD8551 the difference between the simulated and actual transfer functions AD8628 1 of the circuit shown in Figure 52. IN OUT 100kΩ 470pF 1kΩ 0.1 10 100 1k 10k 3dB FILTER BANDWIDTH (Hz) Figure 52. First-Order Low-Pass Filter Test Circuit, Figure 55. RMS Noise vs. 3 dB Filter Bandwidth in Hz ×101 Gain and 3 kHz Corner Frequency Rev. I | Page 15 of 24 VOLTAGE (0.5µV/DIV) VOLTAGE (0.5µV/DIV) 02735-049 02735-048 02735-047 RMS NOISE (µV) NOISE (dB) NOISE (dB) 02735-052 02735-050 02735-051 AD8628/AD8629/AD8630 INPUT OVERVOLTAGE PROTECTION CH1 = 50mV/DIV CH2 = 1V/DIV V IN A = –50 Although the AD8628/AD8629/AD8630 are rail-to-rail input V amplifiers, care should be taken to ensure that the potential difference between the inputs does not exceed the supply voltage. 0V Under normal negative feedback operating conditions, the amplifier corrects its output to ensure that the two inputs are at the same voltage. However, if either input exceeds either supply 0V rail by more than 0.3 V, large currents begin to flow through the ESD protection diodes in the amplifier. These diodes are connected between the inputs and each supply rail to protect the input transistors against an electrostatic discharge V OUT event, and they are normally reverse-biased. However, if the input TIME (500µs/DIV) voltage exceeds the supply voltage, these ESD diodes can become Figure 56. Positive Input Overload Recovery for the AD8628 forward-biased. Without current limiting, excessive amounts of current could flow through these diodes, causing permanent damage to the device. If inputs are subject to overvoltage, CH1 = 50mV/DIV appropriate series resistors should be inserted to limit the diode CH2 = 1V/DIV V IN A = –50 V current to less than 5 mA maximum. OUTPUT PHASE REVERSAL 0V Output phase reversal occurs in some amplifiers when the input common-mode voltage range is exceeded. As common-mode voltage is moved outside the common-mode range, the outputs of 0V these amplifiers can suddenly jump in the opposite direction to the supply rail. This is the result of the differential input pair shutting down, causing a radical shifting of internal voltages that results in the erratic output behavior. V OUT The AD8628/AD8629/AD8630 amplifiers have been carefully TIME (500µs/DIV) designed to prevent any output phase reversal, provided that Figure 57. Positive Input Overload Recovery for Competitor A both inputs are maintained within the supply voltages. If one or both inputs could exceed either supply voltage, a resistor should be placed in series with the input to limit the current to less than CH1 = 50mV/DIV 5 mA. This ensures that the output does not reverse its phase. CH2 = 1V/DIV V IN A = –50 V OVERLOAD RECOVERY TIME Many auto-zero amplifiers are plagued by a long overload recovery 0V time, often in ms, due to the complicated settling behavior of the internal nulling loops after saturation of the outputs. The AD8628/AD8629/AD8630 have been designed so that internal 0V settling occurs within two clock cycles after output saturation occurs. This results in a much shorter recovery time, less than 10 μs, when compared to other auto-zero amplifiers. The wide bandwidth of the AD8628/AD8629/AD8630 enhances V OUT performance when the parts are used to drive loads that inject transients into the outputs. This is a common situation when an TIME (500µs/DIV) amplifier is used to drive the input of switched capacitor ADCs. Figure 58. Positive Input Overload Recovery for Competitor B Rev. I | Page 16 of 24 VOLTAGE (V) VOLTAGE (V) VOLTAGE (V) 02735-055 02735-053 02735-054 AD8628/AD8629/AD8630 The results shown in Figure 56 to Figure 61 are summarized in Table 5. 0V CH1 = 50mV/DIV CH2 = 1V/DIV Table 5. Overload Recovery Time A = –50 V Positive Overload Negative Overload V IN Model Recovery (μs) Recovery (μs) AD8628 6 9 Competitor A 650 25,000 V OUT Competitor B 40,000 35,000 INFRARED SENSORS 0V Infrared (IR) sensors, particularly thermopiles, are increasingly being used in temperature measurement for applications as wide TIME (500µs/DIV) ranging as automotive climate control, human ear thermometers, Figure 59. Negative Input Overload Recovery for the AD8628 home insulation analysis, and automotive repair diagnostics. The relatively small output signal of the sensor demands high gain with very low offset voltage and drift to avoid dc errors. 0V CH1 = 50mV/DIV If interstage ac coupling is used, as in Figure 62, low offset and CH2 = 1V/DIV A = –50 V drift prevent the output of the input amplifier from drifting close to V IN V saturation. The low input bias currents generate minimal errors OUT from the output impedance of the sensor. As with pressure sensors, the very low amplifier drift with time and temperature eliminate additional errors once the temperature measurement is calibrated. 0V The low 1/f noise improves SNR for dc measurements taken over periods often exceeding one-fifth of a second. Figure 62 shows a circuit that can amplify ac signals from 100 μV to 300 μV up to the 1 V to 3 V levels, with a gain of 10,000 for accurate analog-to-digital conversion. 10kΩ 100kΩ TIME (500µs/DIV) 100Ω 100kΩ Figure 60. Negative Input Overload Recovery for Competitor A 5V 5V 100µV TO 300µV 10µF 1/2 AD8629 IR 0V 1/2 AD8629 DETECTOR 10kΩ CH1 = 50mV/DIV f ≈ 1.6Hz C CH2 = 1V/DIV A = –50 V TO BIAS V IN VOLTAGE Figure 62. AD8629 Used as Preamplifier for Thermopile V OUT 0V TIME (500µs/DIV) Figure 61. Negative Input Overload Recovery for Competitor B Rev. I | Page 17 of 24 VOLTAGE (V) VOLTAGE (V) VOLTAGE (V) 02735-057 02735-056 02735-058 02735-059 AD8628/AD8629/AD8630 PRECISION CURRENT SHUNT SENSOR OUTPUT AMPLIFIER FOR HIGH PRECISION DACS A precision current shunt sensor benefits from the unique The AD8628/AD8629/AD8360 are used as output amplifiers for attributes of auto-zero amplifiers when used in a differencing a 16-bit high precision DAC in a unipolar configuration. In this configuration, as shown in Figure 63. Current shunt sensors are case, the selected op amp needs to have a very low offset voltage used in precision current sources for feedback control systems. (the DAC LSB is 38 μV when operated with a 2.5 V reference) They are also used in a variety of other applications, including to eliminate the need for output offset trims. The input bias battery fuel gauging, laser diode power measurement and control, current (typically a few tens of picoamperes) must also be very torque feedback controls in electric power steering, and precision low because it generates an additional zero code error when power metering. multiplied by the DAC output impedance (approximately 6 kΩ). Rail-to-rail input and output provide full-scale output with very R S R SUPPLY L little error. The output impedance of the DAC is constant and 0.1Ω I code independent, but the high input impedance of the AD8628/ 100kΩ 100Ω AD8629/AD8630 minimizes gain errors. The wide bandwidth e = 1000 R I S C 100mV/mA of the amplifiers also serves well in this case. The amplifiers, 5V with settling time of 1 μs, add another time constant to the system, increasing the settling time of the output. The settling AD8628 time of the AD5541 is 1 μs. The combined settling time is approximately 1.4 μs, as can be derived from the following 100kΩ 100Ω equation: C 2 2 t() TOTAL = (t DAC) +(t AD8628) S S S Figure 63. Low-Side Current Sensing In such applications, it is desirable to use a shunt with very low 2.5V 5V 10µF resistance to minimize the series voltage drop; this minimizes wasted power and allows the measurement of high currents 0.1µF 0.1µF while saving power. A typical shunt might be 0.1 Ω. At measured current values of 1 A, the output signal of the shunt is hundreds SERIAL V REF(REFF*) REFS* DD of millivolts, or even volts, and amplifier error sources are not INTERFACE CS critical. However, at low measured current values in the 1 mA AD8628 DIN UNIPOLAR AD5541/AD5542 V range, the 100 μV output voltage of the shunt demands a very OUT OUTPUT SCLK low offset voltage and drift to maintain absolute accuracy. Low LDAC* DGND input bias currents are also needed, so that injected bias current AGND *AD5542 ONLY does not become a significant percentage of the measured current. Figure 64. AD8628 Used as an Output Amplifier High open-loop gain, CMRR, and PSRR help to maintain the overall circuit accuracy. As long as the rate of change of the current is not too fast, an auto-zero amplifier can be used with excellent results. Rev. I | Page 18 of 24 02735-060 02735-061 AD8628/AD8629/AD8630 OUTLINE DIMENSIONS 2.90 BSC 5.00 (0.1968) 4.80 (0.1890) 54 85 6.20 (0.2441) 2.80 BSC 4.00 (0.1574) 1.60 BSC 1 5.80 (0.2284) 3.80 (0.1497) 4 12 3 0.95 BSC 1.27 (0.0500) 0.50 (0.0196) 45° BSC 1.90 1.75 (0.0688) 0.25 (0.0099) * 0.90 MAX BSC 1.35 (0.0532) 0.25 (0.0098) 8° 0.70 MIN 0.10 (0.0040) 0° * COPLANARITY 0.51 (0.0201) 1.00 MAX 0.20 1.27 (0.0500) 0.10 0.31 (0.0122) 0.08 0.25 (0.0098) SEATING 0.40 (0.0157) 8° PLANE 0.17 (0.0067) 0.10 MAX 4° 0.50 SEATING 0.60 PLANE 0° 0.30 0.45 COMPLIANT TO JEDEC STANDARDS MS-012-AA 0.30 CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS * (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR COMPLIANT TO JEDEC STANDARDS MO-193-AB WITH THE EXCEPTION OF PACKAGE HEIGHT AND THICKNESS. REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 65. 5-Lead Thin Small Outline Transistor Package [TSOT] Figure 67. 8-Lead Standard Small Outline Package [SOIC_N] (UJ-5) Narrow Body Dimensions shown in millimeters (R-8) Dimensions shown in millimeters and (inches) 3.00 3.20 2.90 3.00 2.80 2.80 5 4 3.00 1.70 8 5 2.80 5.15 1.60 3.20 2.60 1.50 4.90 123 3.00 4.65 1 2.80 4 0.95 BSC PIN 1 1.90 IDENTIFIER BSC 1.30 0.65 BSC 1.15 0.90 0.95 15° MAX 0.20 MAX 1.45 MAX 0.85 0.08 MIN 1.10 MAX 0.95 MIN 0.75 0.55 0.15 MAX 10° 0.45 0.80 SEATING 0.20 0.05 MIN 0.15 5° 0.23 0.50 MAX 6° 0.35 0.55 PLANE BSC 0.40 0° 0.05 0.09 0.35 MIN 0° 0.40 0.25 COPLANARITY 0.10 COMPLIANT TO JEDEC STANDARDS MO-178-AA COMPLIANT TO JEDEC STANDARDS MO-187-AA Figure 66. 5-Lead Small Outline Transistor Package [SOT-23] Figure 68. 8-Lead Mini Small Outline Package [MSOP] (RJ-5) (RM-8) Dimensions shown in millimeters Dimensions shown in millimeters Rev. I | Page 19 of 24 121608-A 100708-A 10-07-2009-B 012407-A AD8628/AD8629/AD8630 5.10 5.00 8.75 (0.3445) 4.90 8.55 (0.3366) 14 8 14 8 6.20 (0.2441) 4.00 (0.1575) 4.50 1 5.80 (0.2283) 3.80 (0.1496) 7 6.40 4.40 BSC 4.30 1 7 1.27 (0.0500) 0.50 (0.0197) 45° BSC 0.25 (0.0098) 1.75 (0.0689) PIN 1 0.25 (0.0098) 1.35 (0.0531) 8° 0.10 (0.0039) 0° 0.65 BSC COPLANARITY SEATING 1.27 (0.0500) 1.05 0.51 (0.0201) 0.10 PLANE 0.25 (0.0098) 1.20 0.40 (0.0157) 1.00 0.31 (0.0122) 0.17 (0.0067) 0.20 MAX 0.80 0.09 0.75 8° 0.15 0.60 COMPLIANT TO JEDEC STANDARDS MS-012-AB SEATING 0° 0.05 0.45 0.30 CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS PLANE COPLANARITY (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR 0.19 0.10 REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. COMPLIANT TO JEDEC STANDARDS MO-153-AB-1 Figure 69. 14-Lead Standard Small Outline Package [SOIC_N] Figure 70. 14-Lead Thin Shrink Small Outline Package [TSSOP] Narrow Body (R-14) (RU-14) Dimensions shown in millimeters and (inches) Dimensions shown in millimeters Rev. I | Page 20 of 24 060606-A 061908-A AD8628/AD8629/AD8630 ORDERING GUIDE 1, 2 Model Temperature Range Package Description Package Option Branding AD8628AUJ-REEL −40°C to +125°C 5-Lead TSOT UJ-5 AYB AD8628AUJ-REEL7 −40°C to +125°C 5-Lead TSOT UJ-5 AYB AD8628AUJZ-R2 −40°C to +125°C 5-Lead TSOT UJ-5 A0L AD8628AUJZ-REEL −40°C to +125°C 5-Lead TSOT UJ-5 A0L AD8628AUJZ-REEL7 −40°C to +125°C 5-Lead TSOT UJ-5 A0L AD8628ARZ −40°C to +125°C 8-Lead SOIC_N R-8 AD8628ARZ-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8628ARZ-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8628ARTZ-R2 −40°C to +125°C 5-Lead SOT-23 RJ-5 A0L AD8628ARTZ-REEL7 −40°C to +125°C 5-Lead SOT-23 RJ-5 A0L AD8628WARZ-RL −40°C to +125°C 8-Lead SOIC_N R-8 A0L AD8628WARZ-R7 −40°C to +125°C 8-Lead SOIC_N R-8 A0L AD8628WARTZ-RL −40°C to +125°C 5-Lead SOT-23 RJ-5 A0L AD8628WARTZ-R7 −40°C to +125°C 5-Lead SOT-23 RJ-5 A0L AD8628WAUJZ-RL −40°C to +125°C 5-Lead TSOT UJ-5 A0L AD8628WAUJZ-R7 −40°C to +125°C 5-Lead TSOT UJ-5 A0L AD8629ARZ −40°C to +125°C 8-Lead SOIC_N R-8 AD8629ARZ-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8629ARZ-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8629ARMZ −40°C to +125°C 8-Lead MSOP RM-8 A06 AD8629ARMZ-REEL −40°C to +125°C 8-Lead MSOP RM-8 A06 AD8629WARZ-RL −40°C to +125°C 8-Lead SOIC_N R-8 AD8629WARZ-R7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8630ARUZ −40°C to +125°C 14-Lead TSSOP RU-14 AD8630ARUZ-REEL −40°C to +125°C 14-Lead TSSOP RU-14 AD8630ARZ −40°C to +125°C 14-Lead SOIC_N R-14 AD8630ARZ-REEL −40°C to +125°C 14-Lead SOIC_N R-14 AD8630ARZ-REEL7 −40°C to +125°C 14-Lead SOIC_N R-14 AD8630WARZ-RL −40°C to +125°C 14-Lead SOIC_N R-14 AD8630WARZ-R7 −40°C to +125°C 14-Lead SOIC_N R-14 1 Z = RoHS Compliant Part. 2 W = Qualified for Automotive Applications. AUTOMOTIVE PRODUCTS The AD8628W/AD8629W/AD8630W models are available with controlled manufacturing to support the quality and reliability requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in automotive applications. Contact your local Analog Devices account representative for specific product ordering information and to obtain the specific Automotive Reliability reports for these models. Rev. I | Page 21 of 24 AD8628/AD8629/AD8630 NOTES Rev. I | Page 22 of 24 AD8628/AD8629/AD8630 NOTES Rev. I | Page 23 of 24 AD8628/AD8629/AD8630 NOTES ©2002–2011 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D02735-0-4/11(I) Rev. I | Page 24 of 24