ANALOG DEVICES AD8601

Precision CMOS, Single-Supply, Rail-to-Rail, Input/Output Wideband Operational Amplifiers AD8601/AD8602/AD8604 FEATURES PIN CONFIGURATIONS Low offset voltage: 500 μV maximum OUT A 1 5 V+ AD8601 Single-supply operation: 2.7 V to 5.5 V TOP VIEW V– 2 Low supply current: 750 μA/Amplifier (Not to Scale) Wide bandwidth: 8 MHz +IN 3 4 –IN Slew rate: 5 V/μs Figure 1. 5-Lead SOT-23 (RJ Suffix) Low distortion No phase reversal OUT A 1 8 V+ AD8602 –IN A 2 7 OUT B Low input currents TOP VIEW +IN A 3 6 –IN B Unity-gain stable (Not to Scale) V– 4 5 +IN B Qualified for automotive applications Figure 2. 8-Lead MSOP (RM Suffix) and 8-Lead SOIC (R-Suffix) APPLICATIONS OUT A 1 14 OUT D Current sensing –IN A 2 13 –IN D Barcode scanners +IN A 3 AD8604 12 +IN D PA controls TOP VIEW V+ 4 11 V– Battery-powered instrumentation (Not to Scale) 5 +IN B 10 +IN C Multipole filters 6 9 –IN B –IN C Sensors 7 8 OUT B OUT C ASIC input or output amplifiers Audio Figure 3. 14-Lead TSSOP (RU Suffix) and 14-Lead SOIC (R Suffix) GENERAL DESCRIPTION OUT A 1 16 OUT D The AD8601, AD8602, and AD8604 are single, dual, and quad –IN A 2 15 –IN D rail-to-rail, input and output, single-supply amplifiers featuring 3 14 +IN A AD8604 +IN D very low offset voltage and wide signal bandwidth. These amplifiers TOP VIEW 4 13 V+ V– (Not to Scale) use a new, patented trimming technique that achieves superior 5 12 +IN B +IN C performance without laser trimming. All are fully specified to 6 11 –IN B –IN C operate on a 3 V to 5 V single supply. OUT B 7 10 OUT C The combination of low offsets, very low input bias currents, 8 9 NC NC and high speed make these amplifiers useful in a wide variety NC = NO CONNECT of applications. Filters, integrators, diode amplifiers, shunt Figure 4. 16-Lead Shrink Small Outline QSOP (RQ Suffix) current sensors, and high impedance sensors all benefit from the combination of performance features. Audio and other ac The AD8601, AD8602, and AD8604 are specified over the applications benefit from the wide bandwidth and low distortion. extended industrial (−40°C to +125°C) temperature range. The For the most cost-sensitive applications, the D grades offer this AD8601, single, is available in a tiny, 5-lead SOT-23 package. The ac performance with lower dc precision at a lower price point. AD8602, dual, is available in 8-lead MSOP and 8-lead, narrow SOIC surface-mount packages. The AD8604, quad, is available Applications for these amplifiers include audio amplification for in 14-lead TSSOP, 14-lead SOIC, and 16-lead QSOP packages. portable devices, portable phone headsets, bar code scanners, See the Ordering Guide for automotive grades. portable instruments, cellular PA controls, and multipole filters. The ability to swing rail-to-rail at both the input and output enables designers to buffer CMOS ADCs, DACs, ASICs, and other wide output swing devices in single-supply systems. Rev. Rev. G G IIn nffo orma rmattio ion n furn furniish she ed d b by y A An na allo og g D De ev viic ce es s is is be belliie ev ved ed tto o be be a ac cc cu ur ra atte e an and d r re elliia ab ble le. H . Ho ow we ev ve er r,, n no o r res esp pons onsi ib bi il li it ty y i is s a assu ssumed b med by y A An na al log og De Dev vi ic ce es f s fo or it r its use s use, , nor f nor fo or an r any y inf infrin ringe gemen ment ts s o of f p pa at ten ent ts s o or r o ot the her r O One T ne Te echnology chnology Way, Way, P P..O. O. B Bo ox 91 x 9106, 06, Nor Norw wood ood,, MA 020 MA 02062- 62-910 9106, 6, U. U.S S..A. A. r ri ig gh hts o ts of f th thir ird d par part ties ies th tha at t m ma ay y r re esu sul lt t f fr ro om m i it ts s use use. . S Sp pe eci cif fica icat tio ion ns s su subj bje ec ct t t to o c ch han ang ge e w wi ith tho ou ut n t no oti tic ce e. . N No o T Te el: l: 781. 781.329. 329.4 4700 700 w ww ww w. .analog analog.c .com om l li ic ce en ns se e i is s g gr ran ant te ed d b by y imp impl lic ica at tio ion n o or r o ot th he er rw wi is se e un und de er an r any y pa pat te en nt t o or r pa pat te en nt t r ri ig gh ht ts s o of f A An na al lo og g D De ev vi ic ce es s. . Fax: Fax: 781. 781.461. 461.31 3113 13 © ©2000– 2000–20 2011 A 11 Anal nalog Device og Devices, s, I Inc. nc. Al All r l rights r ights re eser served ved. . T Tr radem ademar arks ks and and r reg egi ist ste er red ed tr trad adema emarks rks ar are e the the p pr ro op per ert ty y of of the thei ir r r re esp spe ec ct ti iv ve e o owne wners rs. . 01525-001 01525-002 01525-004 01525-003 AD8601/AD8602/AD8604 TABLE OF CONTENTS Features .............................................................................................. 1  Input Overvoltage Protection ................................................... 16  Applications....................................................................................... 1  Overdrive Recovery ................................................................... 16  General Description ......................................................................... 1  Power-On Time .......................................................................... 16  Pin Configurations ........................................................................... 1  Using the AD8602 in High Source Impedance Applications ................................................................................ 16  Revision History ............................................................................... 2  High Side and Low Side, Precision Current Monitoring ...... 16  Specifications..................................................................................... 3  Using the AD8601 in Single-Supply, Mixed Signal Electrical Characteristics............................................................. 3  Applications ................................................................................ 17  Absolute Maximum Ratings............................................................ 5  PC100 Compliance for Computer Audio Applications ........ 17  Thermal Resistance ...................................................................... 5  SPICE Model............................................................................... 18  ESD Caution.................................................................................. 5  Outline Dimensions....................................................................... 19  Typical Performance Characteristics ............................................. 6  Ordering Guide .......................................................................... 22  Theory of Operation ...................................................................... 15  Automotive Products................................................................. 22  Rail-to-Rail Input Stage ............................................................. 15  REVISION HISTORY 1/11—Rev. F to Rev. G 11/03—Rev. C to Rev. D Changes to Ordering Guide .......................................................... 22 Changes to Features ..........................................................................1 Change to Automotive Products Section .................................... 22 Changes to Ordering Guide .............................................................4 3/03—Rev. B to Rev. C 5/10—Rev. E to Rev. F Changes to Features Section and General Description Changes to Features ..........................................................................1 Section................................................................................................ 1 Changes to Ordering Guide .......................................................... 22 3/03—Rev. A to Rev. B Added Automotive Products Section .......................................... 22 Change to Features............................................................................1 Change to Functional Block Diagrams...........................................1 2/10—Rev. D to Rev. E Change to TPC 39 .......................................................................... 11 Add 16-Lead QSOP............................................................Universal Changes to Figures 4 and 5 ........................................................... 14 Changes to Table 3 and Table 4....................................................... 5 Changes to Equations 2 and 3................................................. 14, 15 Updated Outline Dimensions ....................................................... 19 Updated Outline Dimensions....................................................... 16 Changes to Ordering Guide .......................................................... 22 Rev. G | Page 2 of 24 AD8601/AD8602/AD8604 SPECIFICATIONS ELECTRICAL CHARACTERISTICS V = 3 V, V = V /2, T = 25°C, unless otherwise noted. S CM S A Table 1. A Grade D Grade Parameter Symbol Conditions Min Typ Max Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage (AD8601/AD8602) V 0 V ≤ V ≤ 1.3 V 80 500 1100 6000 μV OS CM −40°C ≤ T ≤ +85°C 700 7000 μV A −40°C ≤ T ≤ +125°C 1100 7000 μV A 1 0 V ≤ VCM ≤ 3 V 350 750 1300 6000 μV −40°C ≤ T ≤ +85°C 1800 7000 μV A −40°C ≤ TA ≤ +125°C 2100 7000 μV Offset Voltage (AD8604) V V = 0 V to 1.3 V 80 600 1100 6000 μV OS CM −40°C ≤ TA ≤ +85°C 800 7000 μV −40°C ≤ TA ≤ +125°C 1600 7000 μV 1 350 800 1300 6000 μV VCM = 0 V to 3.0 V −40°C ≤ T ≤ +85°C 2200 7000 μV A −40°C ≤ TA ≤ +125°C 2400 7000 μV Input Bias Current I 0.2 60 0.2 200 pA B −40°C ≤ TA ≤ +85°C 25 100 25 200 pA −40°C ≤ TA ≤ +125°C 150 1000 150 1000 pA Input Offset Current I 0.1 30 0.1 100 pA OS −40°C ≤ TA ≤ +85°C 50 100 pA −40°C ≤ T ≤ +125°C 500 500 pA A Input Voltage Range 0 3 0 3 V Common-Mode Rejection Ratio CMRR V = 0 V to 3 V 68 83 52 65 dB CM Large Signal Voltage Gain AVO VO = 0.5 V to 2.5 V, 30 100 20 60 V/mV R = 2 kΩ, V = 0 V L CM Offset Voltage Drift ΔVOS/ΔT 2 2 μV/°C OUTPUT CHARACTERISTICS Output Voltage High VOH IL = 1.0 mA 2.92 2.95 2.92 2.95 V –40°C ≤ T ≤ +125°C 2.88 2.88 V A Output Voltage Low VOL IL = 1.0 mA 20 35 20 35 mV −40°C ≤ T ≤ +125°C 50 50 mV A Output Current I ±30 ±30 mA OUT Closed-Loop Output Impedance ZOUT f = 1 MHz, AV = 1 12 12 Ω POWER SUPPLY Power Supply Rejection Ratio PSRR V = 2.7 V to 5.5 V 67 80 56 72 dB S Supply Current/Amplifier ISY VO = 0 V 680 1000 680 1000 μA −40°C ≤ T ≤ +125°C 1300 1300 μA A DYNAMIC PERFORMANCE Slew Rate SR RL = 2 kΩ 5.2 5.2 V/μs Settling Time tS To 0.01% <0.5 <0.5 μs Gain Bandwidth Product GBP 8.2 8.2 MHz Phase Margin Φo 50 50 Degrees NOISE PERFORMANCE Voltage Noise Density en f = 1 kHz 33 33 nV/√Hz f = 10 kHz 18 18 nV/√Hz Current Noise Density in 0.05 0.05 pA/√Hz 1 For V between 1.3 V and 1.8 V, V may exceed specified value. CM OS Rev. G | Page 3 of 24 AD8601/AD8602/AD8604 V = 5.0 V, V = V /2, T = 25°C, unless otherwise noted. S CM S A Table 2. A Grade D Grade Parameter Symbol Conditions Min Typ Max Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage (AD8601/AD8602) V 0 V ≤ V ≤ 5 V 80 500 1300 6000 μV OS CM −40°C ≤ TA ≤ +125°C 1300 7000 μV Offset Voltage (AD8604) VOS VCM = 0 V to 5 V 80 600 1300 6000 μV −40°C ≤ TA ≤ +125°C 1700 7000 μV Input Bias Current I 0.2 60 0.2 200 pA B −40°C ≤ T ≤ +85°C 100 200 pA A −40°C ≤ T ≤ +125°C 1000 1000 pA A Input Offset Current IOS 0.1 30 0.1 100 pA −40°C ≤ TA ≤ +85°C 6 50 6 100 pA −40°C ≤ TA ≤ +125°C 25 500 25 500 pA Input Voltage Range 0 5 0 5 V Common-Mode Rejection Ratio CMRR V = 0 V to 5 V 74 89 56 67 dB CM Large Signal Voltage Gain AVO VO = 0.5 V to 4.5 V, 30 80 20 60 V/mV RL = 2 kΩ, VCM = 0 V Offset Voltage Drift ΔVOS/ΔT 2 2 μV/°C OUTPUT CHARACTERISTICS Output Voltage High VOH IL = 1.0 mA 4.925 4.975 4.925 4.975 V IL = 10 mA 4.7 4.77 4.7 4.77 V −40°C ≤ T ≤ +125°C 4.6 4.6 V A Output Voltage Low V I = 1.0 mA 15 30 15 30 mV OL L I = 10 mA 125 175 125 175 mV L −40°C ≤ TA ≤ +125°C 250 250 mV Output Current IOUT ±50 ±50 mA Closed-Loop Output Impedance ZOUT f = 1 MHz, AV = 1 10 10 Ω POWER SUPPLY Power Supply Rejection Ratio PSRR VS = 2.7 V to 5.5 V 67 80 56 72 dB Supply Current/Amplifier ISY VO = 0 V 750 1200 750 1200 μA −40°C ≤ T ≤ +125°C 1500 1500 μA A DYNAMIC PERFORMANCE Slew Rate SR R = 2 kΩ 6 6 V/μs L Settling Time t To 0.01% <1.0 <1.0 μs S Full Power Bandwidth BWp <1% distortion 360 360 kHz Gain Bandwidth Product GBP 8.4 8.4 MHz Phase Margin Φo 55 55 Degrees NOISE PERFORMANCE Voltage Noise Density en f = 1 kHz 33 33 nV/√Hz f = 10 kHz 18 18 nV/√Hz Current Noise Density in f = 1 kHz 0.05 0.05 pA/√Hz Rev. G | Page 4 of 24 AD8601/AD8602/AD8604 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 3. θ is specified for worst-case conditions, that is, a device JA Parameter Rating soldered onto a circuit board for surface-mount packages using Supply Voltage 6 V a standard 4-layer board. Input Voltage GND to V S Differential Input Voltage ±6 V Table 4. Thermal Resistance Storage Temperature Range −65°C to +150°C Package Type θ θ Unit JA JC Operating Temperature Range −40°C to +125°C 5-Lead SOT-23 (RJ) 190 92 °C/W Junction Temperature Range −65°C to +150°C 8-Lead SOIC (R) 120 45 °C/W Lead Temperature Range (Soldering, 60 sec) 300°C 8-Lead MSOP (RM) 142 45 °C/W ESD 2 kV HBM 14-Lead SOIC (R) 115 36 °C/W 14-Lead TSSOP (RU) 112 35 °C/W Stresses above those listed under Absolute Maximum Ratings 16-Lead QSOP (RQ) 115 36 °C/W may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational ESD CAUTION section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. G | Page 5 of 24 AD8601/AD8602/AD8604 TYPICAL PERFORMANCE CHARACTERISTICS 3,000 60 V = 3V V = 5V S S T = 25°C T = 25°C TO 85°C A A V = 0V TO 3V 2,500 CM 50 2,000 40 1,500 30 1,000 20 500 10 0 0 –1.0 –0.8 –0.6 –0.4 –0.2 0 0.2 0.4 0.6 0.8 1.0 01 2 3 4 5 6 7 8 9 10 INPUT OFFSET VOLTAGE (mV) TCVOS (µV/°C) Figure 5. Input Offset Voltage Distribution Figure 8. Input Offset Voltage Drift Distribution 3,000 1.5 V = 3V S V = 5V S T = 25°C A T = 25°C A 1.0 V = 0V TO 5V 2,500 CM 0.5 2,000 0 1,500 –0.5 1,000 –1.0 500 –1.5 0 –2.0 0 0.5 1.0 1.5 2.0 2.5 3.0 –1.0 –0.8 –0.6 –0.4 –0.2 0 0.2 0.4 0.6 0.8 1.0 INPUT OFFSET VOLTAGE (mV) COMMON-MODE VOLTAGE (V) Figure 6. Input Offset Voltage Distribution Figure 9. Input Offset Voltage vs. Common-Mode Voltage 60 1.5 V = 5V S V = 3V S T = 25°C A T = 25°C TO 85°C A 1.0 50 0.5 40 0 30 –0.5 20 –1.0 10 –1.5 –2.0 0 01 2 3 4 5 6 7 8 9 10 01 2 3 4 5 TCVOS (µV/°C) COMMON-MODE VOLTAGE (V) Figure 7. Input Offset Voltage Drift Distribution Figure 10. Input Offset Voltage vs. Common-Mode Voltage Rev. G | Page 6 of 24 QUANTITY (Amplifiers) QUANTITY (Amplifiers) QUANTITY (Amplifiers) 01525-007 01525-006 01525-005 INPUT OFFSET VOLTAGE (mV) INPUT OFFSET VOLTAGE (mV) QUANTITY (Amplifiers) 01525-008 01525-010 01525-009 AD8601/AD8602/AD8604 300 30 V = 3V V = 3V S S 250 25 200 20 150 15 100 10 50 5 0 0 –40 –25 –105 203550658095 110 125 –40 –25 –105 203550658095 110 125 TEMPERATURE (°C) TEMPERATURE (°C) Figure 11. Input Bias Current vs. Temperature Figure 14. Input Offset Current vs. Temperature 300 30 V = 5V V = 5V S S 250 25 200 20 150 15 100 10 50 5 0 0 –40 –25 –105 203550658095 110 125 –40 –25 –105 203550658095 110 125 TEMPERATURE (°C) TEMPERATURE (°C) Figure 12. Input Bias Current vs. Temperature Figure 15. Input Offset Current vs. Temperature 5 10k V = 2.7V V = 5V S S T = 25°C T = 25°C A A 4 1k 3 100 SOURCE SINK 2 10 1 1 0 0.1 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 0.001 0.01 0.1 1 10 100 COMMON-MODE VOLTAGE (V) LOAD CURRENT (mA) Figure 13. Input Bias Current vs. Common-Mode Voltage Figure 16. Output Voltage to Supply Rail vs. Load Current Rev. G | Page 7 of 24 INPUT BIAS CURRENT (pA) INPUT BIAS CURRENT (pA) INPUT BIAS CURRENT (pA) 01525-013 01525-012 01525-011 OUTPUT VOLTAGE (mV) INPUT OFFSET CURRENT (pA) INPUT OFFSET CURRENT (pA) 01525-015 01525-014 01525-016 AD8601/AD8602/AD8604 10k 35 V = 5V S V = 2.7V S T = 25°C A 30 1k 25 100 20 SOURCE V @ 1mA LOAD OH SINK 15 10 10 1 5 0 0.1 0.001 0.01 0.1 1 10 100 –40 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) LOAD CURRENT (mA) Figure 17. Output Voltage to Supply Rail vs. Load Current Figure 20. Output Voltage Swing vs. Temperature 5.1 2.67 V = 2.7V S V = 5V S 5.0 2.66 V @ 1mA LOAD OH 4.9 2.65 4.8 V @ 1mA LOAD OH 2.64 V @ 10mA LOAD OH 4.7 2.63 4.6 4.5 2.62 –40 –25 –105 203550658095 110 125 –40 –25 –10 5 20 35 50 65 80 95 110 125 TEMPERATURE (°C) TEMPERATURE (°C) Figure 18. Output Voltage Swing vs. Temperature Figure 21. Output Voltage Swing vs. Temperature 250 120 –90 V = 3V V = 5V S S R = NO LOAD 100 –45 L T = 25°C A 0 80 200 45 60 PHASE 90 40 150 V @ 10mA LOAD OH 20 135 180 0 100 GAIN –20 225 270 –40 50 –60 315 V @ 1mA LOAD OH 360 0 –80 –40 –25 –10 5 20 35 50 65 80 95 110 125 1k 10k 100k 1M 10M 100M TEMPERATURE (°C) FREQUENCY (Hz) Figure 19. Output Voltage Swing vs. Temperature Figure 22. Open-Loop Gain and Phase vs. Frequency Rev. G | Page 8 of 24 OUTPUT VOLTAGE (mV) OUTPUT VOLTAGE (V) OUTPUT VOLTAGE (mV) 01525-018 01525-019 01525-017 GAIN (dB) OUTPUT VOLTAGE (V) OUTPUT VOLTAGE (mV) 01525-020 01525-021 PHASE SHIFT (Degrees) 01525-022 AD8601/AD8602/AD8604 120 3.0 –90 V = 5V S R = NO LOAD 100 –45 L T = 25°C A 2.5 0 80 V = 2.7V S V = 2.6V p-p IN 45 60 R = 2kΩ L 2.0 T = 25°C A PHASE 90 40 A = 1 V 20 135 1.5 180 0 GAIN 1.0 –20 225 –40 270 0.5 –60 315 360 –80 0 1k 10k 100k 1M 10M 100M 1k 10k 100k 1M 10M FREQUENCY (Hz) FREQUENCY (Hz) Figure 23. Open-Loop Gain and Phase vs. Frequency Figure 26. Closed-Loop Output Voltage Swing vs. Frequency 6 V = 3V S T = 25°C A A = 100 V 5 40 V = 5V S V = 4.9V p-p IN A = 10 V 4 R = 2kΩ L 20 T = 25°C A A = 1 V 3 A = 1 V 0 2 1 0 1k 10k 100k 1M 10M 100M 1k 10k 100k 1M 10M FREQUENCY (Hz) FREQUENCY (Hz) Figure 27. Closed-Loop Output Voltage Swing vs. Frequency Figure 24. Closed-Loop Gain vs. Frequency 200 V = 5V S V = 3V S T = 25°C A T = 25°C 180 A A = 100 V 40 160 140 A = 10 V A = 100 V 20 120 100 A = 1 V A = 10 V 0 80 60 A = 1 V 40 20 0 1k 10k 100k 1M 10M 100M 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) FREQUENCY (Hz) Figure 25. Closed-Loop Gain vs. Frequency Figure 28. Output Impedance vs. Frequency Rev. G | Page 9 of 24 GAIN (dB) CLOSD-LOOP GAIN (dB) CLOSD-LOOP GAIN (dB) 01525-025 01525-024 PHASE SHIFT (Degrees) 01525-023 OUTPUT IMPEDANCE (Ω) OUTPUT SWING (V p-p) OUTPUT SWING (V p-p) 01525-027 01525-026 01525-028 AD8601/AD8602/AD8604 200 160 V = 5V V = 5V S S T = 25°C T = 25°C 180 140 A A 160 120 100 140 120 80 A = 100 V 60 100 A = 10 V 80 40 A = 1 V 20 60 0 40 –20 20 –40 0 100 1k 10k 100k 1M 10M 100 1k 10k 100k 1M 10M FREQUENCY (Hz) FREQUENCY (Hz) Figure 29. Output Impedance vs. Frequency Figure 32. Power Supply Rejection Ratio vs. Frequency 160 70 V = 2.7V V = 3V S S R = 140 T = 25°C A L ∞ 60 T = 25°C A A = 1 120 V 50 100 –OS 80 40 60 +OS 30 40 20 20 0 10 –20 –40 0 1k 10k 100k 1M 10M 20M 10 100 1k FREQUENCY (Hz) CAPACITANCE (pF) Figure 30. Common-Mode Rejection Ratio vs. Frequency Figure 33. Small Signal Overshoot vs. Load Capacitance 160 70 V = 5V V = 5V S S T = 25°C R = 140 L ∞ A 60 T = 25°C A A = 1 V 120 50 100 80 40 –OS 60 30 40 +OS 20 20 0 10 –20 –40 0 10 100 1k 1k 10k 100k 1M 10M 20M FREQUENCY (Hz) CAPACITANCE (pF) Figure 31. Common-Mode Rejection Ratio vs. Frequency Figure 34. Small Signal Overshoot vs. Load Capacitance Rev. G | Page 10 of 24 COMMON-MODE REJECTION (dB) COMMON-MODE REJECTION (dB) OUTPUT IMPEDANCE (Ω) 01525-029 01525-031 01525-030 POWER SUPPLY REJECTION (dB) SMALL SIGNAL OVERSHOOT (%) SMALL SIGNAL OVERSHOOT (%) 01525-034 01525-033 01525-032 AD8601/AD8602/AD8604 1.2 0.1 V = 5V S V = 5V S T = 25°C A R = 600Ω L 1.0 R = 2kΩ G = 10 L R = 10kΩ L 0.01 0.8 R = 600Ω L R = 2kΩ L 0.6 G = 1 R = 10kΩ L 0.001 0.4 0.2 0 0.0001 20 100 1k 10k 20k –40 –25 –105 203550658095 110 125 TEMPERATURE (°C) FREQUENCY (Hz) Figure 38. Total Harmonic Distortion + Noise vs. Frequency Figure 35. Supply Current per Amplifier vs. Temperature 1.0 64 V = 2.7V S V = 3V S T = 25°C A 56 0.8 48 40 0.6 32 0.4 24 16 0.2 8 0 0 –40 –25 –105 203550658095 110 125 0 5 10 15 20 25 TEMPERATURE (°C) FREQUENCY (kHz) Figure 36. Supply Current per Amplifier vs. Temperature Figure 39. Voltage Noise Density vs. Frequency 0.8 208 V = 2.7V S T = 25°C A 182 0.7 156 0.6 130 0.5 104 0.4 78 0.3 52 0.2 26 0.1 0 0 0 0.5 1.0 1.5 2.0 2.5 01234 5 6 SUPPLY VOLTAGE (V) FREQUENCY (kHz) Figure 40. Voltage Noise Density vs. Frequency Figure 37. Supply Current per Amplifier vs. Supply Voltage Rev. G | Page 11 of 24 SUPPLY CURRENT PER AMPLIFIER (mA) SUPPLY CURRENT PER AMPLIFIER (mA) SUPPLY CURRENT PER AMPLIFIER (mA) 01525-037 01525-036 01525-035 THD + N (%) VOLTAGE NOISE DENSITY (nV/ Hz) VOLTAGE NOISE DENSITY (nV/ Hz) 01525-039 01525-040 01525-038 AD8601/AD8602/AD8604 208 V = 5V S V = 5V S T = 25°C A T = 25°C A 182 156 130 104 78 52 26 0 TIME (1s/DIV) 0 0.5 1.0 1.5 2.0 2.5 FREQUENCY (kHz) Figure 41. Voltage Noise Density vs. Frequency Figure 44. 0.1 Hz to 10 Hz Input Voltage Noise 64 V = 5V S V = 5V S R = 10kΩ L T = 25°C A 56 C = 200pF L T = 25°C A 48 40 32 24 16 8 50mV/DIV 200ns/DIV 0 0 5 10 15 20 25 FREQUENCY (kHz) Figure 42. Voltage Noise Density vs. Frequency Figure 45. Small Signal Transient Response V = 2.7V S V = 2.7V S T = 25°C A R = 10kΩ L C = 200pF L T = 25°C A 50mV/DIV 200ns/DIV TIME (1s/DIV) Figure 46. Small Signal Transient Response Figure 43. 0.1 Hz to 10 Hz Input Voltage Noise Rev. G | Page 12 of 24 VOLTAGE NOISE DENSITY (nV/ Hz) VOLTAGE NOISE DENSITY (nV/ Hz) VOLTAGE (2.5µV/DIV) 01525-043 01525-042 01525-041 VOLTAGE (2.5µV/DIV) 01525-046 01525-045 01525-044 AD8601/AD8602/AD8604 V V = 5V IN V = 5V S S R = 10kΩ R = 10kΩ L L C = 200pF A = 1 L V A = 1 T = 25°C V A T = 25°C A V OUT TIME (400ns/DIV) TIME (2µs/DIV) Figure 47. Large Signal Transient Response Figure 50. No Phase Reversal V = 2.7V V = 5V S S R = 10kΩ R = 10kΩ L L C = 200pF V = 2V p-p L O A = 1 T = 25°C V A T = 25°C A V IN +0.1% ERROR V OUT –0.1% ERROR V TRACE – 0.5V/DIV IN V TRACE – 10mV/DIV OUT TIME (400ns/DIV) TIME (100ns/DIV) Figure 48. Large Signal Transient Response Figure 51. Settling Time 2.0 V = 2.7V S V = 2.7V S R = 10kΩ L T = 25°C A A = 1 1.5 V V IN T = 25°C A 1.0 0.1% 0.01% 0.5 V OUT 0 –0.5 0.1% 0.01% –1.0 –1.5 –2.0 TIME (2µs/DIV) 300 350 400 450 500 550 600 SETTLING TIME (ns) Figure 49. No Phase Reversal Figure 52. Output Swing vs. Settling Time Rev. G | Page 13 of 24 VOLTAGE (1V/DIV) VOLTAGE (500mV/DIV) VOLTAGE (1V/DIV) 01525-049 01525-048 01525-047 VOLTAGE (V) OUTPUT SWING (V) VOLTAGE (1V/DIV) 01525-050 01525-052 01525-051 AD8601/AD8602/AD8604 5 V = 5V S T = 25°C 4 A 3 2 1 0.1% 0.01% 0 0.1% 0.01% –1 –2 –3 –4 –5 0 200 400 600 800 1,000 SETTLING TIME (ns) Figure 53. Output Swing vs. Settling Time Rev. G | Page 14 of 24 OUTPUT SWING (V) 01525-053 AD8601/AD8602/AD8604 THEORY OF OPERATION The AD8601/AD8602/AD8604 family of amplifiers are rail-to-rail The NMOS and PMOS input stages are separately trimmed using input and output, precision CMOS amplifiers that operate from DigiTrim to minimize the offset voltage in both differential pairs. 2.7 V to 5.0 V of the power supply voltage. These amplifiers use Both NMOS and PMOS input differential pairs are active in a Analog Devices, Inc., DigiTrim® technology to achieve a higher 500 mV transition region, when the input common-mode voltage degree of precision than available from most CMOS amplifiers. is between approximately 1.5 V and 1 V below the positive supply DigiTrim technology is a method of trimming the offset voltage voltage. The input offset voltage shifts slightly in this transition of the amplifier after it has been assembled. The advantage in post- region, as shown in Figure 9 and Figure 10 .The common-mode package trimming lies in the fact that it corrects any offset voltages rejection ratio is also slightly lower when the input common- due to the mechanical stresses of assembly. This technology is mode voltage is within this transition band. Compared to the scalable and used with every package option, including the 5-lead Burr-Brown OPA2340UR rail-to-rail input amplifier, shown in SOT-23, providing lower offset voltages than previously achieved in Figure 54, the AD860x, shown in Figure 55, exhibits lower these small packages. offset voltage shift across the entire input common-mode range, including the transition region. The DigiTrim process is completed at the factory and does not 0.7 add additional pins to the amplifier. All AD860x amplifiers are available in standard op amp pinouts, making DigiTrim completely 0.4 transparent to the user. The AD860x can be used in any precision op amp application. 0.1 The input stage of the amplifier is a true rail-to-rail architecture, –0.2 allowing the input common-mode voltage range of the op amp to extend to both positive and negative supply rails. The voltage –0.5 swing of the output stage is also rail-to-rail and is achieved by –0.8 using an NMOS and PMOS transistor pair connected in a common-source configuration. The maximum output voltage –1.1 swing is proportional to the output current, and larger currents limit how close the output voltage can get to the supply rail, –1.4 01 2 3 45 which is a characteristic of all rail-to-rail output amplifiers. V (V) CM With 1 mA of output current, the output voltage can reach Figure 54. Burr-Brown OPA2340UR Input Offset Voltage vs. within 20 mV of the positive rail and within 15 mV of the Common-Mode Voltage, 24 SOIC Units @ 25°C negative rail. At light loads of >100 kΩ, the output swings within ~1 mV of the supplies. 0.7 The open-loop gain of the AD860x is 80 dB, typical, with a load of 2 kΩ. Because of the rail-to-rail output configuration, the gain 0.4 of the output stage and the open-loop gain of the amplifier are 0.1 dependent on the load resistance. Open-loop gain decreases with smaller load resistances. Again, this is a characteristic inherent –0.2 to all rail-to-rail output amplifiers. –0.5 RAIL-TO-RAIL INPUT STAGE The input common-mode voltage range of the AD860x extends –0.8 to both the positive and negative supply voltages. This maximizes –1.1 the usable voltage range of the amplifier, an important feature for single-supply and low voltage applications. This rail-to-rail –1.4 input range is achieved by using two input differential pairs, one 01 2 3 45 V (V) CM NMOS and one PMOS, placed in parallel. The NMOS pair is active at the upper end of the common-mode voltage range, and Figure 55. AD8602AR Input Offset Voltage vs. Common-Mode Voltage, 300 SOIC Units @ 25°C the PMOS pair is active at the lower end. Rev. G | Page 15 of 24 V (mV) V (mV) OS OS 01525-055 01525-054 AD8601/AD8602/AD8604 The current through the photodiode is proportional to the incident INPUT OVERVOLTAGE PROTECTION light power on its surface. The 4.7 MΩ resistor converts this current As with any semiconductor device, if a condition could exist into a voltage, with the output of the AD8601 increasing at 4.7 V/μA. that could cause the input voltage to exceed the power supply, The feedback capacitor reduces excess noise at higher frequencies the device’s input overvoltage characteristic must be considered. by limiting the bandwidth of the circuit to Excess input voltage energizes the internal PN junctions in the AD860x, allowing current to flow from the input to the supplies. 1 BW= (1) 2π() 4.7 MΩ C This input current does not damage the amplifier, provided it is F limited to 5 mA or less. This can be ensured by placing a resistor in Using a 10 pF feedback capacitor limits the bandwidth to series with the input. For example, if the input voltage could approximately 3.3 kHz. exceed the supply by 5 V, the series resistor should be at least 10pF (OPTIONAL) (5 V/5 mA) = 1 kΩ. With the input voltage within the supply rails, a minimal amount of current is drawn into the inputs, 4.7MΩ which, in turn, causes a negligible voltage drop across the series resistor. Therefore, adding the series resistor does not adversely V D1 OUT affect circuit performance. 4.7V/µA AD8601 OVERDRIVE RECOVERY Figure 56. Amplifier Photodiode Circuit Overdrive recovery is defined as the time it takes the output of an amplifier to come off the supply rail when recovering from HIGH SIDE AND LOW SIDE, PRECISION CURRENT an overload signal. This is tested by placing the amplifier in a MONITORING closed-loop gain of 10 with an input square wave of 2 V p-p Because of its low input bias current and low offset voltage, the while the amplifier is powered from either 5 V or 3 V. AD860x can be used for precision current monitoring. The true The AD860x has excellent recovery time from overload conditions. rail-to-rail input feature of the AD860x allows the amplifier to The output recovers from the positive supply rail within 200 ns monitor current on either the high side or the low side. Using both at all supply voltages. Recovery from the negative rail is within amplifiers in an AD8602 provides a simple method for monitoring 500 ns at a 5 V supply, decreasing to within 350 ns when the both current supply and return paths for load or fault detection. device is powered from 2.7 V. Figure 57 and Figure 58 demonstrate both circuits. 3V POWER-ON TIME R2 The power-on time is important in portable applications where 249kΩ MONITOR the supply voltage to the amplifier may be toggled to shut down OUTPUT the device to improve battery life. Fast power-up behavior ensures Q1 2N3904 3V that the output of the amplifier quickly settles to its final voltage, improving the power-up speed of the entire system. When the supply voltage reaches a minimum of 2.5 V, the AD860x settles to R1 1/2 AD8602 100Ω a valid output within 1 μs. This turn-on response time is faster RETURN TO than many other precision amplifiers, which can take tens or GROUND R SENSE hundreds of microseconds for their outputs to settle. 0.1Ω Figure 57. Low-Side Current Monitor USING THE AD8602 IN HIGH SOURCE IMPEDANCE R SENSE I APPLICATIONS L 0.1Ω 3V V+ The CMOS rail-to-rail input structure of the AD860x allows 3V R1 these amplifiers to have very low input bias currents, typically 100Ω 1/2 AD8602 0.2 pA. This allows the AD860x to be used in any application that has a high source impedance or must use large value resistances around the amplifier. For example, the photodiode Q1 amplifier circuit shown in Figure 56 requires a low input bias 2N3905 current op amp to reduce output voltage error. The AD8601 MONITOR OUTPUT minimizes offset errors due to its low input bias current and low R2 2.49kΩ offset voltage. Figure 58. High-Side Current Monitor Rev. G | Page 16 of 24 01525-056 01525-058 01525-057 AD8601/AD8602/AD8604 Voltage drop is created across the 0.1 Ω resistor that is Figure 60 demonstrates how the AD8601 can be used as an proportional to the load current. This voltage appears at the output buffer for the DAC for driving heavy resistive loads. The inverting input of the amplifier due to the feedback correction AD5320 is a 12-bit DAC that can be used with clock frequencies around the op amp. This creates a current through R1, which up to 30 MHz and signal frequencies up to 930 kHz. The rail- in turn, pulls current through R2. For the low side monitor, the to-rail output of the AD8601 allows it to swing within 100 mV monitor output voltage is given by of the positive supply rail while sourcing 1 mA of current. The total current drawn from the circuit is less than 1 mA, or 3 mW ⎡ R ⎤ ⎛ ⎞ SENSE MonitorOutput=3V− R2× ×I (2) from a 3 V single supply. ⎜ ⎟ ⎢ L⎥ R1 ⎣ ⎝ ⎠ ⎦ 3V For the high side monitor, the monitor output voltage is 1µF R ⎛ ⎞ SENSE V 4 OUT MonitorOutput= R2× ×I (3) ⎜ ⎟ 5 L 0V TO 3V 4 1 R1 ⎝ ⎠ 3-WIRE 3 5 1 SERIAL AD5320 2 R AD8601 6 L Using the components shown, the monitor output transfer INTERFACE function is 2.5 V/A. Figure 60. Using the AD8601 as a DAC Output Buffer to Drive Heavy Loads USING THE AD8601 IN SINGLE-SUPPLY, MIXED SIGNAL APPLICATIONS The AD8601, AD7476, and AD5320 are all available in space- saving SOT-23 packages. Single-supply, mixed signal applications requiring 10 or more bits of resolution demand both a minimum of distortion and a PC100 COMPLIANCE FOR COMPUTER AUDIO maximum range of voltage swing to optimize performance. To APPLICATIONS ensure that the ADCs or DACs achieve their best performance, an Because of its low distortion and rail-to-rail input and output, amplifier often must be used for buffering or signal conditioning. the AD860x is an excellent choice for low cost, single-supply The 750 μV maximum offset voltage of the AD8601 allows the audio applications, ranging from microphone amplification amplifier to be used in 12-bit applications powered from a 3 V to line output buffering. Figure 38 shows the total harmonic single supply, and its rail-to-rail input and output ensure no distortion plus noise (THD + N) figures for the AD860x. In signal clipping. unity gain, the amplifier has a typical THD + N of 0.004%, or Figure 59 shows the AD8601 used as an input buffer amplifier −86 dB, even with a load resistance of 600 Ω. This is compliant to the AD7476, a 12-bit, 1 MSPS ADC. As with most ADCs, with the PC100 specification requirements for audio in both total harmonic distortion (THD) increases with higher source portable and desktop computers. impedances. By using the AD8601 in a buffer configuration, the Figure 61 shows how an AD8602 can be interfaced with an AC’97 low output impedance of the amplifier minimizes THD while codec to drive the line output. Here, the AD8602 is used as a the high input impedance and low bias current of the op amp unity-gain buffer from the left and right outputs of the AC’97 minimizes errors due to source impedance. The 8 MHz gain codec. The 100 μF output coupling capacitors block dc current bandwidth product of the AD8601 ensures no signal attenua- and the 20 Ω series resistors protect the amplifier from short tion up to 500 kHz, which is the maximum Nyquist frequency circuits at the jack. for the AD7476. 5V 5V REF193 SUPPLY 1µF V 25 DD 5V 0.1µF 10µF 0.1µF 680nF TANT C1 R4 2 V 8 29 100µF DD 20Ω 1 A 4 3 5 V SCLK LEFT DD 35 OUT R2 4 1 V R 2kΩ S IN 3 SDATA µC/µP AD1881 2 AD8602 GND (AC’97) CS C2 AD7476/AD7477 R5 AD8601 5 100µF RIGHT 36 20Ω OUT 7 SERIAL B 6 INTERFACE V 26 R3 SS 2kΩ Figure 59. A Complete 3 V 12-Bit 1 MHz Analog-to-Digital Conversion System AD8602 NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. Figure 61. A PC100-Compliant Line Output Amplifier Rev. G | Page 17 of 24 01525-059 + + 01525-061 01525-060 AD8601/AD8602/AD8604 SPICE MODEL The SPICE macro-model for the AD860x amplifier can be down- loaded at www.analog.com. The model accurately simulates a number of both dc and ac parameters, including open-loop gain, bandwidth, phase margin, input voltage range, output voltage swing vs. output current, slew rate, input voltage noise, CMRR, PSRR, and supply current vs. supply voltage. The model is optimized for performance at 27°C. Although it functions at different temperatures, it may lose accuracy with respect to the actual behavior of the AD860x. Rev. G | Page 18 of 24 AD8601/AD8602/AD8604 OUTLINE DIMENSIONS 3.00 2.90 2.80 5 4 3.00 1.70 2.80 1.60 2.60 1.50 12 3 0.95 BSC 1.90 BSC 1.30 1.15 0.90 0.20 MAX 1.45 MAX 0.08 MIN 0.95 MIN 0.55 0.15 MAX 10° 0.45 SEATING 0.60 0.05 MIN 5° 0.50 MAX 0.35 PLANE BSC 0° 0.35 MIN COMPLIANT TO JEDEC STANDARDS MO-178-AA Figure 62. 5-Lead Small Outline Transistor Package [SOT-23] (RJ-5) Dimensions shown in millimeters 3.20 3.00 2.80 8 5 5.15 3.20 4.90 3.00 4.65 1 2.80 4 PIN 1 IDENTIFIER 0.65 BSC 0.95 15° MAX 0.85 1.10 MAX 0.75 0.80 0.15 0.23 6° 0.55 0.40 0.05 0.09 0° 0.40 0.25 COPLANARITY 0.10 COMPLIANT TO JEDEC STANDARDS MO-187-AA Figure 63. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters Rev. G | Page 19 of 24 10-07-2009-B 11-01-2010-A AD8601/AD8602/AD8604 5.00 (0.1968) 4.80 (0.1890) 85 6.20 (0.2441) 4.00 (0.1574) 1 5.80 (0.2284) 3.80 (0.1497) 4 1.27 (0.0500) 0.50 (0.0196) 45° BSC 1.75 (0.0688) 0.25 (0.0099) 1.35 (0.0532) 0.25 (0.0098) 8° 0.10 (0.0040) 0° COPLANARITY 0.51 (0.0201) 1.27 (0.0500) 0.10 0.31 (0.0122) 0.25 (0.0098) SEATING 0.40 (0.0157) PLANE 0.17 (0.0067) COMPLIANT TO JEDEC STANDARDS MS-012-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 64. 8-Lead Standard Small Outline Package [SOIC_N] (R-8) Dimensions shown in millimeters and (inches) 8.75 (0.3445) 8.55 (0.3366) 8 14 6.20 (0.2441) 4.00 (0.1575) 1 5.80 (0.2283) 3.80 (0.1496) 7 1.27 (0.0500) 0.50 (0.0197) 45° BSC 0.25 (0.0098) 1.75 (0.0689) 0.25 (0.0098) 1.35 (0.0531) 8° 0.10 (0.0039) 0° COPLANARITY SEATING 1.27 (0.0500) 0.51 (0.0201) 0.10 PLANE 0.25 (0.0098) 0.40 (0.0157) 0.31 (0.0122) 0.17 (0.0067) COMPLIANT TO JEDEC STANDARDS MS-012-AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 65. 14-Lead Standard Small Outline Package [SOIC_N] (R-14) Dimensions shown in millimeters and (inches) Rev. G | Page 20 of 24 012407-A 060606-A AD8601/AD8602/AD8604 5.10 5.00 4.90 14 8 4.50 6.40 4.40 BSC 4.30 1 7 PIN 1 0.65 BSC 1.05 1.20 1.00 0.20 MAX 0.80 0.09 0.75 0.15 8° 0.60 SEATING 0° 0.05 0.45 0.30 PLANE COPLANARITY 0.19 0.10 COMPLIANT TO JEDEC STANDARDS MO-153-AB-1 Figure 66. 14-Lead Thin Shrink Small Outline Package [TSSOP] (RU-14) Dimensions shown in millimeters 0.197 (5.00) 0.193 (4.90) 0.189 (4.80) 16 9 0.158 (4.01) 0.154 (3.91) 0.244 (6.20) 0.150 (3.81) 1 0.236 (5.99) 8 0.228 (5.79) 0.010 (0.25) 0.020 (0.51) 0.069 (1.75) 0.065 (1.65) 0.006 (0.15) 0.010 (0.25) 0.053 (1.35) 0.049 (1.25) 0.010 (0.25) 0.041 (1.04) SEATING 8° 0.004 (0.10) REF PLANE 0.025 (0.64) 0.050 (1.27) 0° COPLANARITY BSC 0.012 (0.30) 0.016 (0.41) 0.004 (0.10) 0.008 (0.20) COMPLIANT TO JEDEC STANDARDS MO-137-AB CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 67. 16-Lead Shrink Small Outline Package [QSOP] (RQ-16) Dimensions shown in inches and (millimeters) Rev. G | Page 21 of 24 061908-A 01-28-2008-A AD8601/AD8602/AD8604 ORDERING GUIDE 1, 2 Model Temperature Range Package Description Package Option Branding AD8601ARTZ-R2 −40°C to +125°C 5-Lead SOT-23 RJ-5 AAA AD8601ARTZ-REEL −40°C to +125°C 5-Lead SOT-23 RJ-5 AAA AD8601ARTZ-REEL7 −40°C to +125°C 5-Lead SOT-23 RJ-5 AAA AD8601WARTZ-RL −40°C to +125°C 5-Lead SOT-23 RJ-5 AAA AD8601WARTZ-R7 −40°C to +125°C 5-Lead SOT-23 RJ-5 AAA AD8601WDRTZ-REEL −40°C to +125°C 5-Lead SOT-23 RJ-5 AAD AD8601WDRTZ-REEL7 −40°C to +125°C 5-Lead SOT-23 RJ-5 AAD AD8602AR −40°C to +125°C 8-Lead SOIC_N R-8 AD8602AR-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8602AR-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8602ARZ −40°C to +125°C 8-Lead SOIC_N R-8 AD8602ARZ-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8602ARZ-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8602WARZ-RL −40°C to +125°C 8-Lead SOIC_N R-8 AD8602WARZ-R7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8602ARM-REEL −40°C to +125°C 8-Lead MSOP RM-8 ABA AD8602ARMZ −40°C to +125°C 8-Lead MSOP RM-8 ABA AD8602ARMZ-REEL −40°C to +125°C 8-Lead MSOP RM-8 ABA AD8602DR −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DR-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DR-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DRZ −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DRZ-REEL −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DRZ-REEL7 −40°C to +125°C 8-Lead SOIC_N R-8 AD8602DRM-REEL −40°C to +125°C 8-Lead MSOP RM-8 ABD AD8602DRMZ-REEL −40°C to +125°C 8-Lead MSOP RM-8 ABD AD8604ARZ −40°C to +125°C 14-Lead SOIC_N R-14 AD8604ARZ-REEL −40°C to +125°C 14-Lead SOIC_N R-14 AD8604ARZ-REEL7 −40°C to +125°C 14-Lead SOIC_N R-14 AD8604DRZ −40°C to +125°C 14-Lead SOIC_N R-14 AD8604DRZ-REEL −40°C to +125°C 14-Lead SOIC_N R-14 AD8604ARUZ −40°C to +125°C 14-Lead TSSOP RU-14 AD8604ARUZ-REEL −40°C to +125°C 14-Lead TSSOP RU-14 AD8604DRU −40°C to +125°C 14-Lead TSSOP RU-14 AD8604DRU -REEL −40°C to +125°C 14-Lead TSSOP RU-14 AD8604DRUZ −40°C to +125°C 14-Lead TSSOP RU-14 AD8604DRUZ-REEL −40°C to +125°C 14-Lead TSSOP RU-14 AD8604ARQZ −40°C to +125°C 16-Lead QSOP RQ-16 AD8604ARQZ-RL −40°C to +125°C 16-Lead QSOP RQ-16 AD8604ARQZ-R7 −40°C to +125°C 16-Lead QSOP RQ-16 1 Z = RoHS Compliant Part. 2 W = Qualified for Automotive Applications. AUTOMOTIVE PRODUCTS The AD8601W/AD8602W models are available with controlled manufacturing to support the quality and reliability requirements of automotive applications. Note that these automotive models may have specifications that differ from the commercial models; therefore, designers should review the Specifications section of this data sheet carefully. Only the automotive grade products shown are available for use in automotive applications. Contact your local Analog Devices Account Representative for specific product ordering information and to obtain the specific Automotive Reliability reports for these models. Rev. G | Page 22 of 24 AD8601/AD8602/AD8604 NOTES Rev. G | Page 23 of 24 AD8601/AD8602/AD8604 NOTES ©200–2011 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D01525-0-1/11(G) Rev. G | Page 24 of 24