ANALOG DEVICES AD7891

2 LC MOS 8-Channel, 12-Bit a High Speed Data Acquisition System AD7891 FEATURES FUNCTIONAL BLOCK DIAGRAM Fast 12-Bit ADC with 1.6�s Conversion Time REF OUT/ V V 8 Single-Ended Analog Input Channels DD DD REF IN REF GND Overvoltage Protection on Each Channel V IN1A Selection of Input Ranges: 2.5V V IN1B REFERENCE �5 V, �10 V for AD7891-1 STANDBY V IN2A AD7891 V 0 to +2.5 V, 0 to +5 V, �2.5 V for AD7891-2 IN2B V IN3A Parallel and Serial Interface V IN3B On-Chip Track/Hold Amplifier V 12-BIT IN4A M ADC V On-Chip Reference IN4B U V X IN5A Single-Supply, Low Power Operation (100 mW Max) V IN5B Power-Down Mode (75�W Typ) TRACK/HOLD V IN6A V IN6B APPLICATIONS DATA/ V ADDRESS IN7A CONTROL V DECODE Data Acquisition Systems IN7B LINES V IN8A Motor Control V IN8B Mobile Communication Base Stations CLOCK CONTROL LOGIC Instrumentation WR CS RD EOC CONVST MODE AGND AGND DGND GENERAL DESCRIPTION PRODUCT HIGHLIGHTS The AD7891 is an 8-channel, 12-bit data acquisition system 1. The AD7891 is a complete monolithic 12-bit data acquisition with a choice of either parallel or serial interface structure. The system that combines an 8-channel multiplexer, 12-bit ADC, part contains an input multiplexer, an on-chip track/hold ampli- 2.5 V reference, and track/hold amplifier on a single chip. fier, a high speed 12-bit ADC, a 2.5 V reference, and a high 2. The AD7891-2 features a conversion time of 1.6 ms and an speed interface. The part operates from a single 5 V supply and acquisition time of 0.4 ms. This allows a sample rate of accepts a variety of analog input ranges across two models, the 500 kSPS when sampling one channel and 62.5 kSPS when AD7891-1 (±5V and ±10 V) and the AD7891-2 (0 V to +2.5 V, channel hopping. These sample rates can be achieved using 0V to +5 V, and ±2.5 V). either a software or hardware convert start. The AD7891-1 The AD7891 provides the option of either a parallel or serial has an acquisition time of 0.6 ms when using a hardware interface structure determined by the MODE pin. The part convert start and an acquisition time of 0.7 ms when using a has standard control inputs and fast data access times for both software convert start. These acquisition times allow sample the serial and parallel interfaces, ensuring easy interfacing to rates of 454.5 kSPS and 435 kSPS, respectively, for hardware modern microprocessors, microcontrollers, and digital signal and software convert start. processors. 3. Each channel on the AD7891 has overvoltage protection. This In addition to the traditional dc accuracy specifications, such as means an overvoltage on an unselected channel does not affect linearity, full-scale and offset errors, the part is also specified for the conversion on a selected channel. The AD7891-1 can dynamic performance parameters, including harmonic distortion withstand overvoltages of ±17 V. and signal-to-noise ratio. Power dissipation in normal mode is 82 mW typical; in the standby mode, this is reduced to 75 mW typ. The part is available in a 44-terminal MQFP and a 44-lead PLCC. REV. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. may result from its use. No license is granted by implication or otherwise Tel: 781/329-4700 www.analog.com under any patent or patent rights of Analog Devices. Trademarks and Fax: 781/326-8703 © 2004 Analog Devices, Inc. All rights reserved. registered trademarks are the property of their respective owners. (V = 5 V � 5%, AGND = DGND = 0 V, REF IN = 2.5 V. All specifications T to T , DD MIN MAX unless otherwise noted.) AD7891–SPECIFICATIONS 1 Parameter A Version B Version Y Version Unit Test Conditions/Comments 2 3 DYNAMIC PERFORMANCE Sample Rate = 454.5 kSPS (AD7891-1), 3 500 kSPS (AD7891-2). Any channel. 4 Signal-to-(Noise + Distortion) Ratio @ 25∞C707070dB min T to T 70 70 70 dB min MIN MAX 4 Total Harmonic Distortion –78 –78 –78 dB max 4 Peak Harmonic or Spurious Noise –80 –80 –80 dB max 4 Intermodulation Distortion fa = 9 kHz, fb = 9.5 kHz. Second-Order Terms –80 –80 –80 dB typ Third-Order Terms –80 –80 –80 dB typ 4 Channel-to-Channel Isolation –80 –80 –80 dB max DC ACCURACY Any channel. Resolution 12 12 12 Bits Minimum Resolution for which No Missing Codes Are Guaranteed 12 12 12 Bits 4 Relative Accuracy ±1 ±0.75 ±1 LSB max 4 Differential Nonlinearity ±1 ±1 ±1 LSB max 4 Positive Full-Scale Error ±3 ±3 ±3 LSB max 4, 5 Positive Full-Scale Error Match 0.6 0.6 0.6 LSB typ 1.5 LSB max. Unipolar Offset Error ±4 ±4 ±4 LSB max Input ranges of 0 V to 2.5 V, 0 V to 5 V. 5 Unipolar Offset Error Match 0.1 0.1 0.1 LSB typ 1 LSB max. 4 Negative Full-Scale Error ±3 ±3 ±3 LSB max Input ranges of ±2.5 V, ±5V, ±10 V. 4, 5 Negative Full-Scale Error Match 0.6 0.6 0.6 LSB typ 1.5 LSB max. Bipolar Zero Error ±4 ±4 ±4 LSB max Input ranges of ±2.5 V, ±5V, ±10 V. 5 Bipolar Zero Error Match 0.2 0.2 0.2 LSB typ 1.5 LSB max. ANALOG INPUTS AD7891-1 Input Voltage Range ±5 ±5 ±5V Input applied to both V and V . INXA INXB ±10 ±10 ±10 V Input applied to V , V = AGND. INXA INXB AD7891-1 V Input Resistance 7.5 7.5 7.5 kW min Input range of ±5V. INXA AD7891-1 V Input Resistance 15 15 15 kW min Input range of ±10 V. INXA AD7891-2 Input Voltage Range 0 to 2.5 0 to 2.5 0 to 2.5 V Input applied to both V and V . INXA INXB 0 to 5 0 to 5 0 to 5 V Input applied to V , V = AGND. INXA INXB 6 ±2.5 ±2.5 ±2.5 V Input applied to V , V = REF IN . INXA INXB AD7891-2 V Input Resistance 1.5 1.5 1.5 kW min Input ranges of ±2.5 V and 0 V to 5 V. INXA AD7891-2 V Input Current ±50 ±50 ±50 nA max Input range of 0 V to 2.5 V. INXA REFERENCE INPUT/OUTPUT REF IN Input Voltage Range 2.375/2.625 2.375/2.625 2.375/2.625 V min/V max 2.5 V ± 5%. Input Impedance 1.6 1.6 1.6 kW min Resistor connected to internal reference node. 5 Input Capacitance 10 10 10 pF max REF OUT Output Voltage 2.5 2.5 2.5 V nom REF OUT Error @ 25∞C ±10 ±10 ±10 mV max T to T ±20 ±20 ±20 mV max MIN MAX REF OUT Temperature Coefficient 25 25 25 ppm/∞C typ REF OUT Output Impedance 5 5 5 kW nom See REF IN input impedance. LOGIC INPUTS Input High Voltage, V 2.4 2.4 2.4 V min V = 5 V ± 5%. INH DD Input Low Voltage, V 0.8 0.8 0.8 V max V = 5 V ± 5%. INL DD Input Current, I ±10 ±10 ±10 mA max INH 5 Input Capacitance C 10 10 10 pF max IN REV. D –2– AD7891 1 Parameter A Version B Version Y Version Unit Test Conditions/Comments LOGIC OUTPUTS Output High Voltage, V 4.0 4.0 4.0 V min I = 200 mA. OH SOURCE Output Low Voltage, V 0.4 0.4 0.4 V max I = 1.6 mA. OL SINK DB11to DB0 Floating-State Leakage Current ±10 ±10 ±10 mA max 5 Floating-State Capacitance 15 15 15 pF max Output Coding Straight (Natural) Binary Data format bit of control register = 0. Twos Complement Data format bit of control register = 1. CONVERSION RATE Conversion Time 1.6 1.6 1.6 ms max Track/Hold Acquisition Time 0.6 0.6 0.6 ms max AD7891-1 hardware conversion. 0.7 0.7 0.7 ms max AD7891-1 software conversion. 0.4 0.4 0.4 ms max AD7891-2. POWER REQUIREMENTS V 55 5 V nom ±5% for specified performance. DD I DD Normal Mode 20 20 21 mA max Standby Mode 80 80 80 mA max Logic inputs = 0 V or V . DD Power Dissipation V = 5 V. DD Normal Mode 100 100 105 mW max Typically 82 mW. Standby Mode 400 400 400 mW max Typically 75 mW. NOTES 1 Temperature ranges for the A and B Versions: –40∞C to +85∞C. Temperature range for the Y Version: –55∞C to +105∞C. 2 The AD7891-1’s dynamic performance (THD and SNR) and the AD7891-2’s THD are measured with an input frequency of 10 kHz. The AD7891-2’s SNR is evaluated with an input frequency of 100 kHz. 3 This throughput rate can only be achieved when the part is operated in the parallel interface mode. Maximum achievable throughput rate in the serial interface mode is 357 kSPS. 4 See the Terminology section. 5 Sample tested during initial release and after any redesign or process change that may affect this parameter. 6 REF IN must be buffered before being applied to V . INXB Specifications subject to change without notice. ABSOLUTE MAXIMUM RATINGS* Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . 150∞C (T = 25∞C, unless otherwise noted) A MQFP Package, Power Dissipation . . . . . . . . . . . . . . 450 mW q Thermal Impedance . . . . . . . . . . . . . . . . . . . . . . 95∞C/W V to AGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V JA DD Lead Temperature, Soldering V to DGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V DD Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . . . 215∞C Analog Input Voltage to AGND Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . . 220∞C AD7891-1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±17 V PLCC Package, Power Dissipation . . . . . . . . . . . . . . 500 mW AD7891-2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . –5 V, +10 V q Thermal Impedance . . . . . . . . . . . . . . . . . . . . . . 55∞C/W Reference Input Voltage to AGND . . . . –0.3 V to V + 0.3 V JA DD Lead Temperature, Soldering Digital Input Voltage to DGND . . . . . . –0.3 V to V + 0.3 V DD Vapor Phase (60 sec) . . . . . . . . . . . . . . . . . . . . . . . . 215∞C Digital Output Voltage to DGND . . . . . –0.3 V to V + 0.3 V DD Infrared (15 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . . 220∞C Operating Temperature Range Commercial (A, B Versions) . . . . . . . . . . . –40∞C to +85∞C *Stresses above those listed under Absolute Maximum Ratings may cause perma- nent damage to the device. This is a stress rating only; functional operation of the Automotive (Y Version) . . . . . . . . . . . . . . –55∞C to +105∞C device at these or any other conditions above those listed in the operational Storage Temperature Range . . . . . . . . . . . . –65∞C to +150∞C sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD7891 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality. REV. D –3– AD7891 1, 2 TIMING CHARACTERISTICS Parameter A, B, Y Versions Unit Test Conditions/Comments t 1.6 ms max Conversion Time CONV Parallel Interface t 0 ns min CS to RD/WR Setup Time 1 t 35 ns min Write Pulse Width 2 t 25 ns min Data Valid to Write Setup Time 3 t 5 ns min Data Valid to Write Hold Time 4 t 0 ns min CS to RD/WR Hold Time 5 t 35 ns min CONVST Pulse Width 6 t 55 ns min EOC Pulse Width 7 t 35 ns min Read Pulse Width 8 3 t 25 ns min Data Access Time after Falling Edge of RD 9 4 t 5 ns min Bus Relinquish Time after Rising Edge of RD 10 30 ns max Serial Interface t 30 ns min RFS Low to SCLK Falling Edge Setup Time 11 3 t 20 ns max RFS Low to Data Valid Delay 12 t 25 ns min SCLK High Pulse Width 13 t 25 ns min SCLK Low Pulse Width 14 3 t 5 ns min SCLK Rising Edge to Data Valid Hold Time 15 3 t 15 ns max SCLK Rising Edge to Data Valid Delay 16 t 20 ns min RFS to SCLK Falling Edge Hold Time 17 4 t 0 ns min Bus Relinquish Time after Rising Edge of RFS 18 30 ns max 4 t 0 ns min Bus Relinquish Time after Rising Edge of SCLK 18A 30 ns max t 20 ns min TFS Low to SCLK Falling Edge Setup Time 19 t 15 ns min Data Valid to SCLK Falling Edge Setup Time 20 t 10 ns min Data Valid to SCLK Falling Edge Hold Time 21 t 30 ns min TFS Low to SCLK Falling Edge Hold Time 22 NOTES 1 Sample tested during initial release and after any redesign or process change that may affect this parameter. All input signals are measured with tr = tf = 1 ns (10% to 90% of 5 V) and timed from a voltage level of 1.6 V. 2 See Figures 2, 3, and 4. 3 Measured with the load circuit of Figure 1 and defined as the time required for an output to cross 0.8 V or 2.4 V. 4 These times are derived from the measured time taken by the data outputs to change 0.5 V when loaded with the circuit of Figure 1. The measured number is then extrapolated back to remove the effects of charging or discharging the 50 pF capacitor. This means that the times quoted in the timing characteristics are the true bus relinquish times of the part and as such are independent of external bus loading capacitances. Specifications subject to change without notice. 1.6mA TO 1.6V OUTPUT PIN 50pF 200�A Figure 1. Load Circuit for Access Time and Bus Relinquish Time REV. D –4– AD7891 ORDERING GUIDE Relative Temperature 1 Model Input Range Sample Rate Accuracy Range Package Option AD7891ACHIPS-1 DIE AD7891ACHIPS-2 DIE AD7891AS-1 ±5 V or ±10 V 454 kSPS ±1 LSB –40∞C to +85∞CS-44 2 AD7891ASZ-1 ±5 V or ±10 V 454 kSPS ±1 LSB –40∞C to +85∞CS-44 AD7891AP-1 ±5 V or ±10 V 454 kSPS ±1 LSB –40∞C to +85∞C P-44A AD7891AP-1REEL ±5 V or ±10 V 454 kSPS ±1 LSB –40∞C to +85∞C P-44A AD7891BS-1 ±5 V or ±10 V 454 kSPS ±0.75 LSB –40∞C to +85∞CS-44 AD7891BP-1 ±5 V or ±10 V 454 kSPS ±0.75 LSB –40∞C to +85∞C P-44A AD7891BP-1REEL ±5 V or ±10 V 454 kSPS ±0.75 LSB –40∞C to +85∞C P-44A AD7891YS-1 ±5 V or ±10 V 454 kSPS ±1 LSB –55∞C to +105∞CS-44 AD7891YS-1REEL ±5 V or ±10 V 454 kSPS ±1 LSB –55∞C to +105∞CS-44 AD7891YP-1 ±5 V or ±10 V 454 kSPS ±1 LSB –55∞C to +105∞C P-44A AD7891YP-1REEL ±5 V or ±10 V 454 kSPS ±1 LSB –55∞C to +105∞C P-44A AD7891AS-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –40∞C to +85∞CS-44 2 AD7891ASZ-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –40∞C to +85∞CS-44 AD7891AP-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –40∞C to +85∞C P-44A AD7891AP-2REEL 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –40∞C to +85∞C P-44A AD7891BS-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±0.75 LSB –40∞C to +85∞CS-44 AD7891BP-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±0.75 LSB –40∞C to +85∞C P-44A AD7891BP-2REEL 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±0.75 LSB –40∞C to +85∞C P-44A AD7891YS-2 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –55∞C to +105∞CS-44 AD7891YS-2REEL 0 V to +5 V, 0 V to +2.5 V, ±2.5 V 500 kSPS ±1 LSB –55∞C to +105∞CS-44 EVAL-AD7891-1CB Evaluation Board EVAL-AD7891-2CB Evaluation Board NOTES 1 S = Plastic Quad Flatpack (MQFP); P = Plastic Leaded Chip Carrier (PLCC). 2 Z = Pb-free part. PIN CONFIGURATIONS PLCC MQFP 44 43 42 41 40 39 38 37 36 35 34 6 543 21 4443 42 41 40 PIN 1 REF GND 1 33 REF GND 7 39 V V IDENTIFIER IN6A IN6A PIN 1 NC 32 NC 8 38 V 2 V IDENTIFIER IN6B IN6B REF OUT/REF IN 9 37 V REF OUT/REF IN 3 31 V IN7A IN7A V V 10 36 4 30 V V DD DD IN7B IN7B AGND 11 35 AGND 5 29 V V IN8A IN8A AD7891 AD7891 34 MODE 6 28 MODE 12 V V TOP VIEW IN8B TOP VIEW IN8B DB11/TEST 7 27 DB11/TEST 13 (Not to Scale) 33 AGND (Not to Scale) AGND 26 DB10/TEST 14 32 EOC DB10/TEST 8 EOC 15 31 NC DB9/TFS 9 25 NC DB9/TFS 16 30 DB8/RFS 10 24 DB8/RFS CONVST CONVST DB7/DATA IN 17 29 DB7/DATA IN 11 23 CS CS 12 13 14 15 16 17 18 19 20 21 22 18 19 20 21 22 23 24 25 26 27 28 NC = NO CONNECT NC = NO CONNECT REV. D –5– DB6/SCLK STANDBY V V DD IN1A DGND V IN1B DB5/A2/DATA OUT V IN2A DB4/A1 V IN2B DB3/A0 V IN3A DB2/SWCON V IN3B DB1/SWSTBY V IN4A DB0/FORMAT V IN4B V WR IN5A RD V IN5B DB6/SCLK STANDBY V V DD IN1A DGND V IN1B DB5/A2/DATA OUT V IN2A V DB4/A1 IN2B V DB3/A0 IN3A V DB2/SWCON IN3B V DB1/SWSTBY IN4A DB0/FORMAT V IN4B WR V IN5A RD V IN5B AD7891 PIN FUNCTION DESCRIPTIONS PLCC MQFP Pin No. Pin No. Mnemonic Description 1–528–43 V , V Analog Input Channels. The AD7891 contains eight pairs of analog input channels. Each INXA INXB 34–44 channel contains two input pins to allow a number of different input ranges to be used with the AD7891. There are two possible input voltage ranges on the AD7891-1. The ±5V input range is selected by connecting the input voltage to both V and V , INXA INXB while the ±10 V input range is selected by applying the input voltage to V and con- INXA necting V to AGND. The AD7891-2 has three possible input ranges. The 0 V to INXB 2.5 V input range is selected by connecting the analog input voltage to both V and V ; the INXA INXB 0V to 5 V input range is selected by applying the input voltage to V and connecting INXA V to AGND while the ±2.5 V input range is selected by connecting the analog input INXB voltage to V and connecting V to REF IN (provided this REF IN voltage comes INXA INXB from a low impedance source). The channel to be converted is selected by the A2, A1, and A0 bits of the control register. In the parallel interface mode, these bits are available as three data input lines (DB3 to DB5) in a parallel write operation. While in the serial inter- face mode, these three bits are accessed via the DATA IN line in a serial write operation. The multiplexer has guaranteed break-before-make operation. 10, 19 4, 13 V Positive Supply Voltage, 5 V ± 5%. DD 11, 33 5, 27 AGND Analog Ground. Ground reference for track/hold, comparator, and DAC. 20 14 DGND Digital Ground. Ground reference for digital circuitry. 644 STANDBY Standby Mode Input. TTL compatible input used to put the device into the power save or standby mode. The STANDBY input is high for normal operation and low for standby operation. 93 REF OUT/REF IN Voltage Reference Output/Input. The part can either be used with its own internal refer- ence or with an external reference source. The on-chip 2.5 V reference voltage is pro- vided at this pin. When using this internal reference as the reference source for the part, REF OUT should be decoupled to REF GND with a 0.1 mF disc ceramic capaci- tor. The output impedance of the reference source is typically 2 kW. When using an external reference source as the reference voltage for the part, the reference source should be connected to this pin. This overdrives the internal reference and provides the reference source for the part. The reference pin is buffered on-chip but must be able to sink or source current through this 2 kW resistor to the output of the on-chip reference. The nominal reference voltage for correct operation of the AD7891 is 2.5 V. 71 REF GND Reference Ground. Ground reference for the part’s on-chip reference buffer. The REF OUT pin of the part should be decoupled with a 0.1 mF capacitor to this REF GND pin. If the AD7891 is used with an external reference, the external reference should also be decoupled to this pin. The REF GND pin should be connected to the AGND pin or the system’s AGND plane. 30 24 CONVST Convert Start. Edge-triggered logic input. A low-to-high transition on this input puts the track/hold into hold and initiates conversion. When changing channels on the part, sufficient time should be given for multiplexer settling and track/hold acquisition between the channel change and the rising edge of CONVST. 32 26 EOC End-of-Conversion. Active low logic output indicating converter status. The end of con- version is signified by a low-going pulse on this line. The duration of this EOC pulse is nominally 80 ns. 12 6 MODE Interface Mode. Control input that determines the interface mode for the part. With this pin at a logic low, the AD7891 is in its serial interface mode; with this pin at a logic high, the device is in its parallel interface mode. REV. D –6– AD7891 PARALLEL INTERFACE MODE FUNCTIONS PLCC Pin No. MQFP Pin No. Mnemonic Description 8, 31 2, 25 NC No Connect. The two NC pins on the device can be left unconnected. If they are to be connected to a voltage, it should be to ground potential. To ensure correct operation of the AD7891, neither of the NC pins should be connected to a logic high potential. 29 23 CS Chip Select Input. Active low logic input that is used in conjunction with to enable the data outputs and with WR to allow input data to be written to the part. 28 22 RD Read Input. Active low logic input that is used in conjunction with CS low to enable the data outputs. 27 21 WR Write Input. Active low logic input used in conjunction with CS to latch the mul- tiplexer address and software control information. The rising edge of this input also initiates an internal pulse. When using the software start facility, this pulse delays the point at which the track/hold goes into hold and conversion is initiated. This allows the multiplexer to settle and the acquisition time of the track/hold to elapse when a channel address is changed. If the SWCON bit of the control regis- ter is set to 1, when this pulse times out, the track/hold then goes into hold and conversion is initiated. If the SWCON bit of the control register is set to 0, the track/hold and conversion sequence are unaffected by WR operation. Data I/O Lines There are 12 data input/output lines on the AD7891. When the part is configured for parallel mode (MODE = 1), the output data from the part is provided at these 12 pins during a read operation. For a write operation in parallel mode, these lines provide access to the part’s control register. Parallel Read Operation During a parallel read operation, the 12 lines become the 12 data bits containing the conversion result from the AD7891. These data bits are labelled Data Bit 0 (LSB) to Data Bit 11 (MSB). They are three-state, TTL compatible outputs. Output data coding is twos complement when the data FORMAT bit of the control register is 1, and straight binary when the data FORMAT bit of the control register is 0. PLCC Pin No. MQFP Pin No. Mnemonic Description 13 to 18, 7 to 12, DB0 to DB11 Data Bit 0 (LSB) to Data Bit 11 (MSB). Three-state TTL compatible 21 to 26 15 to 20 outputs that are controlled by the CS and RD inputs. Parallel Write Operation During a parallel write operation, the following functions can be written to the control register via the 12 data input/output pins. PLCC Pin No. MQFP Pin No. Mnemonic Description 23 17 A0 Address Input. The status of this input during a parallel write operation is latched to the A0 bit of the control register (see Control Register section). 22 16 A1 Address Input. The status of this input during a parallel write operation is latched to the A1 bit of the control register (see Control Register section). 21 15 A2 Address Input. The status of this input during a parallel write operation is latched to the A2 bit of the control register (see Control Register section). 24 18 SWCON Software Conversion Start. The status of this input during a parallel write operation is latched to the SWCONV bit of the control register (see Control Register section). 25 19 SWSTBY Software Standby Control. The status of this input during a parallel write operation is latched to the SWSTBY bit of the control register (see Control Register section). 26 20 FORMAT Data Format Selection. The status of this input during a parallel write operation is latched to the FORMAT bit of the control register (see Control Register section). REV. D –7– AD7891 SERIAL INTERFACE MODE FUNCTIONS When the part is configured for serial mode (MODE = 0), five of the 12 data input/output lines provide serial interface functions. These functions are outlined below. PLCC Pin No. MQFP Pin No. Mnemonic Description 18 12 SCLK Serial Clock Input. This is an externally applied serial clock that is used to load serial data to the control register and to access data from the output register. 15 9 TFS Transmit Frame Synchronization Pulse. Active low logic input with serial data expected after the falling edge of this signal. 16 10 RFS Receive Frame Synchronization Pulse. This is an active low logic input with RFS provided externally as a strobe or framing pulse to access serial data from the output register. For applications that require that data be transmitted and received at the same time, RFS and TFS should be connected together. 21 15 DATA OUT Serial Data Output. Sixteen bits of serial data are provided with the data FORMAT bit and the three address bits of the control register preceding the 12 bits of conversion data. Serial data is valid on the falling edge of SCLK for 16 edges after RFS goes low. Output conversion data coding is twos complement when the FORMAT bit of the control register is 1 and straight binary when the FORMAT bit of the control register is 0. 17 11 DATA IN Serial Data Input. Serial data to be loaded to the control register is provided at this input. The first six bits of serial data are loaded to the control register on the first six falling edges of SCLK after TFS goes low. Serial data on subsequent SCLK edges is ignored while TFS remains low. 13, 14 7, 8 TEST Test Pin. When the device is configured for serial mode of operation, two of the pins which had been data inputs become test inputs. To ensure correct operation of the device, both TEST inputs should be tied to a logic low potential. CONTROL REGISTER The control register for the AD7891 contains six bits of information as described below. These six bits can be written to the control register either in a parallel mode write operation or via a serial mode write operation. The default (power-on) condition of all bits in the control register is 0. Six serial clock pulses must be provided to the part in order to write data to the control register. If TFS returns high before six serial clock cycles, no data transfer takes place to the control register and the write cycle has to be restarted to write data to the control register. However, if the SWCONV bit of the register was previously set to a Logic 1 and TFS is brought high before six serial clock cycles, another conversion is initiated. LSB (DB0) A1 2A0AVSY WCONST WSTB FORMA A2 Address Input. This input is the most significant address input for multiplexer channel selection. A1 Address Input. This is the second most significant address input for multiplexer channel selection. A0 Address Input. Least significant address input for multiplexer channel selection. When the address is written to the control register, an internal pulse is initiated to allow for the multiplexer settling time and track/hold acquisi- tion time before the track/hold goes into hold and conversion is initiated. When the internal pulse times out, the track/hold goes into hold and conversion is initiated. The selected channel is given by the formula AA 24 ¥+ 1¥+ 2A0+1 SWCONV Conversion Start. Writing a 1 to this bit initiates a conversion in a similar manner to the CONVST input. Con- tinuous conversion starts do not take place when there is a 1 in this location. The internal pulse and the conver- sion process are initiated when a 1 is written to this bit. With a 1 in this bit, the hardware conversion start, i.e., the CONVST input, is disabled. Writing a 0 to this bit enables the hardware CONVST input. SWSTBY Standby Mode Input. Writing a 1 to this bit places the device in its standby or power-down mode. Writing a 0 to this bit places the device in its normal operating mode. FORMAT Data Format. Writing a 0 to this bit sets the conversion data output format to straight (natural) binary. This data format is generally used for unipolar input ranges. Writing a 1 to this bit sets the conversion data output format to twos complement. This output data format is generally used for bipolar input ranges. REV. D –8– AD7891 TERMINOLOGY Channel-to-Channel Isolation Signal-to-(Noise + Distortion) Ratio Channel-to-channel isolation is a measure of the level of This is the measured ratio of signal to (noise + distortion) at the crosstalk between channels. It is measured by applying a full- output of the ADC. The signal is the rms amplitude of the scale 20 kHz (AD7891-1) or 100 kHz (AD7891-2) sine wave fundamental. Noise is the rms sum of all nonfundamental signal to one input channel and determining how much that signals up to half the sampling frequency (f /2), excluding dc. signal is attenuated in each of the other channels. The figure S The ratio is dependent upon the number of quantization levels given is the worst case across all eight channels. in the digitization process; the more levels, the smaller the quan- Relative Accuracy tization noise. The theoretical signal-to-(noise +distortion) ratio Relative accuracy or endpoint nonlinearity is the maximum for an ideal N-bit converter with a sine wave input is given by deviation from a straight line passing through the endpoints of Signal-to-(Noise + Distortion) = (6.02N + 1.76) dB the ADC transfer function. Therefore, for a 12-bit converter, this is 74 dB. Differential Nonlinearity This is the difference between the measured and the ideal 1 LSB Total Harmonic Distortion (THD) change between any two adjacent codes in the ADC. THD is the ratio of the rms sum of harmonics to the fundamental. For the AD7891, it is defined as Positive Full-Scale Error (AD7891-1, �10 V and �5 V; AD7891-2, �2.5 V) 2222 2 This is the deviation of the last code transition (01. . .110 to V ++++ VVVV 2345 6 THD dB = 20log () 01. . .111) from the ideal 4 ¥ REF IN – 3/2 LSB (AD7891-1 V 1 ±10 V range), 2 ¥ REF IN – 3/2 LSB (AD7891-1 ± 5V range), or REF IN – 3/2 LSB (AD7891-2, ±2.5 V range), after the where V is the rms amplitude of the fundamental and V , V , 1 2 3 bipolar zero error has been adjusted out. V , V and V are the rms amplitudes of the second through the 4 5 6 sixth harmonics. Positive Full-Scale Error (AD7891-2, 0 V to 5 V and 0 V to 2.5 V) This is the deviation of the last code transition (11. . .110 to Peak Harmonic or Spurious Noise 11. . .111) from the ideal 2 ¥ REF IN – 3/2 LSB (0 V to 5 V Peak harmonic or spurious noise is defined as the ratio of the rms range), or REF IN – 3/2 LSB (0 V to 2.5 V range), after the value of the next largest component in the ADC output spectrum unipolar offset error has been adjusted out. (up to f /2 and excluding dc) to the rms value of the fundamental. S Normally, the value of this specification is determined by the larg- Bipolar Zero Error (AD7891-1, �10 V and �5 V; AD7891-2, �2.5 V) est harmonic in the spectrum, but for parts where the harmonics This is the deviation of the midscale transition (all 0s to all 1s) are buried in the noise floor, it is a noise peak. from the ideal AGND – 1/2 LSB. Intermodulation Distortion Unipolar Offset Error (AD7891-2, 0 V to 5 V and 0 V to 2.5 V) With inputs consisting of sine waves at two frequencies, fa and This is the deviation of the first code transition (00. . .000 to fb, any active device with nonlinearities creates distortion 00. . .001) from the ideal AGND + 1/2 LSB. products at sum and difference frequencies of mfa ± nfb, where Negative Full-Scale Error (AD7891-1, �10 V and �5 V; m, n = 0, 1, 2, 3, and so on. Intermodulation terms are those for AD7891-2, �2.5 V) which neither m nor n are equal to zero. For example, the This is the deviation of the first code transition (10. . .000 to second-order terms include (fa + fb) and (fa – fb), while the 10. . .001) from the ideal –4 ¥ REF IN + 1/2 LSB (AD7891-1 third-order terms include (2fa + fb), (2fa – fb), (fa + 2fb), and ±10 V range), –2 ¥ REF IN + 1/2 LSB (AD7891-1 ± 5V range), (fa – 2fb). or –REF IN + 1/2 LSB (AD7891-2, ±2.5 V range), after bipolar The AD7891 is tested using the CCIF standard where two zero error has been adjusted out. input frequencies near the top end of the input bandwidth are Track/Hold Acquisition Time used. In this case, the second- and third-order terms are of Track/hold acquisition time is the time required for the output of different significance. The second-order terms are usually dis- the track/hold amplifier to reach its final value, within ±1/2 LSB, tanced in frequency from the original sine waves while the third- after the end of conversion (the point at which the track/hold order terms are usually at a frequency close to the input returns to track mode). It also applies to situations where a frequencies. As a result, the second- and-third order terms are change in the selected input channel takes place or where there specified separately. The calculation of the intermodulation is a step input change on the input voltage applied to the selected distortion is as per the THD specification where it is the ratio of V input of the AD7891. It means the user must wait for the IN the rms sum of the individual distortion products to the rms duration of the track/hold acquisition time after the end of amplitude of the fundamental expressed in dBs. conversion or after a channel change/step input change to V IN before starting another conversion, to ensure the part operates to specification. REV. D –9– AD7891 CONVERTER DETAILS INTERFACE INFORMATION The AD7891 is an 8-channel, high speed, 12-bit data acquisi- The AD7891 provides two interface options, a 12-bit parallel tion system. It provides the user with signal scaling, multiplexer, interface and a high speed serial interface. The required inter- track/hold, reference, ADC, and high speed parallel and serial face mode is selected via the MODE pin. The two interface interface logic functions on a single chip. The signal condition- modes are discussed in the following sections. ing on the AD7891-1 allows the part to accept analog input Parallel Interface Mode ranges of ±5V or ±10 V when operating from a single supply. The parallel interface mode is selected by tying the MODE The input circuitry on the AD7891-2 allows the part to handle input to a logic high. Figure 2 shows a timing diagram illustrating input signal ranges of 0 V to +2.5 V, 0 V to +5 V, and ±2.5 V the operational sequence of the AD7891 in parallel mode for a again while operating from a single 5 V supply. The part requires hardware conversion start. The multiplexer address is written to a 2.5 V reference that can be provided from the part’s own internal the AD7891 on the rising edge of the WR input. The on-chip reference or from an external reference source. track/hold goes into hold mode on the rising edge of CONVST; Conversion is initiated on the AD7891 either by pulsing the conversion is also initiated at this point. When the conversion is CONVST input or by writing a Logic 1 to the SWCONV bit of complete, the end of conversion line (EOC) pulses low to indi- the control register. When using the hardware CONVST input, cate that new data is available in the AD7891’s output register. the on-chip track/hold goes from track to hold mode and the This EOC line can be used to drive an edge-triggered interrupt conversion sequence is started on the rising edge of the CONVST of a microprocessor. CS and RD going low accesses the 12-bit signal. When a software conversion start is initiated, an internal conversion result. In systems where the part is interfaced to a pulse is generated, delaying the track/hold acquisition point and gate array or ASIC, this EOC pulse can be applied to the CS the conversion start sequence until the pulse is timed out. This and RD inputs to latch data out of the AD7891 and into the internal pulse is initiated (goes from low to high) whenever a gate array or ASIC. This means the gate array or ASIC does not write to the AD7891 control register takes place with a 1 in the need any conversion status recognition logic, and it also elimi- SWCONV bit. It then starts to discharge and the track/hold nates the logic required in the gate array or ASIC to generate cannot go into hold and conversion cannot be initiated until the the read signal for the AD7891. pulse signal goes low. The internal pulse duration is equal to the track/hold acquisition time. This allows the user to obtain a CONVST (I) valid result after changing channels and initiating a conversion t t 6 7 in the same write operation. EOC (O) The conversion clock for the part is internally generated and t CONV conversion time for the AD7891 is 1.6 ms from the rising edge of the hardware CONVST signal. The track/hold acquisition time CS (O) for the AD7891-1 is 600 ns, while the track/hold acquisition t t t t 1 5 1 5 t t 2 8 time for the AD7891-2 is 400 ns. To obtain optimum perfor- mance from the part, the data read operation should not occur WR (I) during the conversion or during the 100 ns prior to the next conversion. This allows the AD7891-1 to operate at throughput RD (I) t 3 t rates up to 454.5 kSPS and the AD7891-2 to operate at through- 9 t 4 t 10 put rates up to 500 kSPS in the parallel mode and achieve data DB0 TO DB11 VALID DATA VALID DATA INPUT OUTPUT (I/O) sheet specifications. In the serial mode, the maximum achievable NOTE throughput rate for both the AD7891-1 and the AD7891-2 is I = INPUT 357 kSPS (assuming a 20 MHz serial clock). O = OUTPUT All unused analog inputs should be tied to a voltage within the Figure 2. Parallel Mode Timing Diagram nominal analog input range to avoid noise pickup. For mini- mum power consumption, the unused analog inputs should be tied to AGND. REV. D –10– AD7891 Serial Interface Mode remain low for the duration of the data transfer operation. Six- The serial interface mode is selected by tying the MODE input teen bits of data are transmitted in serial mode with the data to a logic low. In this case, five of the data/control inputs of the FORMAT bit first, followed by the three address bits in the parallel mode assume serial interface functions. control register, followed by the 12-bit conversion result starting with the MSB. Serial data is clocked out of the device on the The serial interface on the AD7891 is a 5-wire interface with rising edge of SCLK and is valid on the falling edge of SCLK. read and write capabilities, with data being read from the output At the end of the read operation, the DATA OUT line is three- register via the DATA OUT line and data being written to the stated by a rising edge on either the SCLK or RFS inputs, which- control register via the DATA IN line. The part operates in a ever occurs first. slave or external clocking mode and requires an externally applied serial clock to the SCLK input to access data from the data Write Operation register or write data to the control register. There are separate Figure 4 shows a write operation to the control register of the framing signals for the read (RFS) and write (TFS) operations. AD7891. The TFS input goes low to indicate to the part that a The serial interface on the AD7891 is designed to allow the part serial write is about to occur. The AD7891 control register to be interfaced to systems that provide a serial clock that is requires only six bits of data. These are loaded on the first six synchronized to the serial data, such as the 80C51, 87C51, clock cycles of the serial clock with data on all subsequent clock 68HC11, and 68HC05, and most digital signal processors. cycles being ignored. Serial data to be written to the AD7891 must be valid on the falling edge of SCLK. When using the AD7891 in serial mode, the data lines DB11 to DB10 should be tied to logic low, and the CS, WR, and RD Simplifying the Serial Interface inputs should be tied to logic high. Pins DB4 to DB0 can be To minimize the number of interconnect lines to the AD7891 tied to either logic high or logic low but must not be left floating in serial mode, the user can connect the RFS and TFS lines because this condition could cause the AD7891 to draw of the AD7891 together and read and write from the part simul- large amounts of current. taneously. In this case, a new control register data line selecting the input channel and providing a conversion start command Read Operation should be provided on the DATA IN line, while the part pro- Figure 3 shows the timing diagram for reading from the AD7891 vides the result from the conversion just completed on the in serial mode. RFS goes low to access data from the AD7891. DATA OUT line. The serial clock input does not have to be continuous. The serial data can be accessed in a number of bytes. However, RFS must RFS (I) t t 11 t 13 17 SCLK (I) t t 14 18 t 12 t t t 18A 15 16 THREE-STATE DATA OUT (O) FORMAT A2 A1 A0 DB11 DB10 DB0 NOTE I = INPUT O = OUTPUT Figure 3. Serial Mode Read Operation TFS (I) t t 19 22 SCLK (I) t 21 t 20 DON'T DON'T DATA IN (I) A0 A1 A0 CONV STBY FORMAT CARE CARE NOTE I = INPUT Figure 4. Serial Mode Write Operation REV. D –11– AD7891 CIRCUIT DESCRIPTION The input resistance for the ±5 V range is typically 20 kW. For Reference the ±10 V input range, the input resistance is typically 34.3 kW. The AD7891 contains a single reference pin labeled REF OUT/ The resistor input stage is followed by the multiplexer, which is REF IN that either provides access to the part’s own 2.5 V followed by the high input impedance stage of the track/hold internal reference or to which an external 2.5 V reference can be amplifier. connected to provide the reference source for the part. The part The designed code transitions take place midway between suc- is specified with a 2.5 V reference voltage. Errors in the reference cessive integer LSB values (i.e., 1/2 LSB, 3/2 LSBs, 5/2 LSBs). source result in gain errors in the transfer function of the AD7891 LSB size is given by the formula 1 LSB = F /4096. Therefore, for S and add to the specified full-scale errors on the part. They also the ±5 V range, 1 LSB = 10 V/4096 = 2.44 mV. For the ±10 V result in an offset error injected into the attenuator stage. range, 1 LSB = 20 V/4096 = 4.88 mV. Output coding is deter- The AD7891 contains an on-chip 2.5 V reference. To use this mined by the FORMAT bit of the control register. The ideal reference as a reference source for the AD7891, simply connect input/output code transitions are shown in Table I. a 0.1 mF disc ceramic capacitor from the REF OUT/REF IN pin AD7891-2 to REFGND. REFGND should be connected to AGND or the Figure 6 shows the analog input section of the AD7891-2. Each analog ground plane. The voltage that appears at the REF OUT/ input can be configured for input ranges of 0 V to +5 V, 0 V to +2.5 V, REF IN pin is internally buffered before being applied to the or ±2.5 V. For the 0 V to 5 V input range, the V input is INXB ADC. If this reference is required for use external to the AD7891, tied to AGND and the input voltage is applied to the V input. INXA it should be buffered since the part has a FET switch in series For the 0 V to 2.5 V input range, the V and V inputs INXA INXB with the reference, resulting in a source impedance for this are tied together and the input voltage is applied to both. For output of 2 kW nominal. The tolerance of the internal reference the ±2.5 V input range, the V input is tied to 2.5 V and INXB is ±10 mV at 25∞C with a typical temperature coefficient of the input voltage is applied to the V input. The 2.5 V source INXA 25 ppm/∞C and a maximum error over temperature of ±20 mV. must have a low output impedance. If the internal reference on If the application requires a reference with a tighter tolerance the AD7891 is used, it must be buffered before being applied to or if the AD7891 needs to be used with a system reference, an V . The V and V inputs are symmetrical and fully INXB INXA INXB external reference can be connected to the REF OUT/REF IN interchangeable. Therefore, for ease of PCB layout on the 0 V to +5 V pin. The external reference overdrives the internal reference or ±2.5 V range, the input voltage may be applied to the V INXB and thus provides the reference source for the ADC. The refer- input, while the V input is tied to AGND or 2.5 V. INXA ence input is buffered before being applied to the ADC and REF OUT/REF IN the maximum input current is ±100 mA. Suitable reference for the AD7891 include the AD580, the AD680, the AD780, and TO ADC the REF43 precision 2.5 V references. REFERENCE CIRCUITRY 2k� Analog Input Section 1.8k� V INXA The AD7891 is offered as two part types: the AD7891-1 where 1.8k� 2.5V each input can be configured to have a ±10 V or a ±5 V input TO V INXB REFERENCE MULTIPLEXER range, and the AD7891-2 where each input can be configured AD7891-2 to have a 0 V to +2.5 V, 0 V to +5 V, and ±2.5 V input range. AGND AD7891-1 Figure 5 shows the analog input section of the AD7891-1. Each Figure 6. AD7891-2 Analog Input Structure input can be configured for ±5 V or ±10 V operation. For 5 V The input resistance for both the 0 V to +5 V and ±2.5 V ranges operation, the V and V inputs are tied together and the INXA INXB is typically 3.6 kW. When an input is configured for 0 V to 2.5 V input voltage is applied to both. For ±10 V operation, the V INXB operation, the input is fed into the high impedance stage of the input is tied to AGND and the input voltage is applied to the track/hold amplifier via the multiplexer and the two 1.8 kW V input. The V and V inputs are symmetrical and INXA INXA INXB resistors in parallel. fully interchangeable. Therefore, for ease of PCB layout on the ±10 V range, the input voltage may be applied to the V INXB The designed code transitions occur midway between successive input while the V input is tied to AGND. INXA integer LSB values (i.e., 1/2 LSB, 3/2 LSBs, 5/2 LSBs). LSB size is given by the formula 1 LSB = F /4096. Therefore, for the 0 V S REF OUT/REF IN to 5 V range, 1 LSB = 5 V/4096 = 1.22 mV, for the 0 V to 2.5 V TO ADC range, 1 LSB = 2.5 V/4096 = 0.61 mV, and for the ±2.5 V range, REFERENCE CIRCUITRY 1 LSB = 5 V/4096 = 1.22 mV. Output coding is determined by 30k� 7.5k� V INXA the FORMAT bit in the control register. The ideal input/output 2k� code transitions for the ±2.5 V range are shown in Table I. The 30k� ideal input/output code transitions for the 0 V to 5 V range and TO V INXB MULTIPLEXER 2.5V the 0 V to 2.5 V range are shown in Table II. REFERENCE 15k� AD7891-1 AGND Figure 5. AD7891-1 Analog Input Structure REV. D –12– AD7891 Table I. Ideal Code Transition Table for the AD7891-1, �10 V and �5 V Ranges and the AD7891-2, �2.5 V Range 1 Digital Output Code Transition Analog Input Input Voltage Twos Complement Straight Binary 2 3 4 +FSR /2 – 3/2 LSB (9.99268 V, 4.99634 V or 2.49817 V) 011...110 to 011...111 111...110 to 111...111 +FSR/2 – 5/2 LSB (9.98779 V, 4.99390 V or 2.49695 V) 011...101 to 011...110 111...101 to 111...110 +FSR/2 – 7/2 LSB (9.99145 V, 4.99146 V or 2.49573 V) 011...100 to 011...101 111...100 to 111...101 AGND + 3/2 LSB (7.3242 mV, 3.6621 mV or 1.8310 mV) 000...001 to 000...010 100...001 to 100...010 AGND + 1/2 LSB (2.4414 mV, 1.2207 mV or 0.6103 mV) 000...000 to 000...001 100...000 to 100...001 AGND – 1/2 LSB (–2.4414 mV, –1.2207 mV or –0.6103 mV) 111...111 to 000...000 011...111 to 100...000 AGND – 3/2 LSB (–7.3242 mV, –3.6621 mV or –1.8310 mV) 111...110 to 111...111 011...110 to 011...111 –FSR/2 + 5/2 LSB (–9.98779 V, –4.99390 V or –2.49695 V) 100...010 to 100...011 000...010 to 000...011 –FSR/2 + 3/2 LSB (–9.99268 V, –4.99634 V or –2.49817 V) 100...001 to 100...010 000...001 to 000...010 –FSR/2 + 1/2 LSB (–9.99756 V, –4.99878 V or –2.49939 V) 100...000 to 100...001 000...000 to 000...001 NOTES 1 Output code format is determined by the FORMAT bit in the control register. 2 FSR is full-scale range and is +20 V for the ±10 V range, +10 V for the ±5 V range, and +5 V for the ±2.5 V range, with REF IN = +2.5 V. 3 1 LSB = FSR/4096 = +4.88 mV ( ±10 V range), +2.44 mV (±5 V range), and +1.22 mV (±2.5 V range), with REF IN = +2.5 V. 4 ±10 V range, ±5 V range, or ±2.5 V range. Table II. Ideal Code Transition Table for the AD7891-2, 0 V to 5 V and 0 V to 2.5 V Ranges 1 Digital Output Code Transition Analog Input Input Voltage Twos Complement Straight Binary 2 3 4 +FSR – 3/2 LSB (4.99817 V or 2.49908 V) 011...110 to 011...111 111...110 to 111...111 +FSR – 5/2 LSB (4.99695 V or 2.49847 V) 011...101 to 011...110 111...101 to 111...110 +FSR – 7/2 LSB (4.99573 V or 2.49786 V) 011...100 to 011...101 111...100 to 111...101 AGND + 5/2 LSB (3.0518 mV or 1.52588 mV) 100...010 to 000...011 000...010 to 000...011 AGND + 3/2 LSB (1.83105 mV or 0.9155 mV) 100...001 to 000...010 000...001 to 000...010 AGND + 1/2 LSB (0.6103 mV or 0.3052 mV) 100...000 to 000...001 000...000 to 000...001 NOTES 1 Output code format is determined by the FORMAT bit in the control register. 2 FSR is the full-scale range and is 5 V for the 0 to 5 V range and 2.5 V for the 0 to 2.5 V range, with REF IN = 2.5 V. 3 1 LSB = F /4096 = 1.22 mV (0 to 5 V range) or 610 mV (0 to 2.5 V range), with REF IN = 2.5 V. S 4 0 V to 5 V range or 0 V to 2.5 V range. Transfer Function of the AD7891-1 and AD7891-2 Table III. Transfer Function M and N Values The transfer function of the AD7891-1 and AD7891-2 can be Range Output Data Format M N expressed as AD7891-1 Input Voltage=¥ M REF IN¥ D/4096+¥ N REF IN ()() ±10 V Straight Binary 8 –4 ±10 V Twos Complement 8 0 D is the output data from the AD7891 and is in the range 0 to ±5 V Straight Binary 4 –2 4095 for straight binary encoding and from –2048 to +2047 for ±5 V Twos Complement 4 0 twos complement encoding. Values for M depend upon the AD7891-2 input voltage range. Values for N depend upon the input voltage 0 V to +5 V Straight Binary 2 0 range and the output data format. These values are given in 0 V to +5 V Twos Complement 2 1 Table III. REF IN is the reference voltage applied to the AD7891. 0 V to +2.5 V Straight Binary 1 0 0 V to +2.5 V Twos Complement 1 0.5 ±2.5 V Straight Binary 2 –1 ±2.5 V Twos Complement 2 0 REV. D –13– AD7891 Track/Hold Amplifier P3.4 The track/hold amplifier on the AD7891 allows the ADC to RFS accurately convert an input sine wave of full-scale amplitude P3.3 TFS AD7891* 8X51* to 12-bit accuracy. The input bandwidth of the track/hold is TXD SCLK greater than the Nyquist rate of the ADC even when the ADC is RXD DATA IN operated at its maximum throughput rate of 454 kHz (AD7891-1) or 500 kHz (AD7891-2). In other words, the track/hold amplifier DATA OUT can handle input frequencies in excess of 227 kHz (AD7891-1) *ADDITIONAL PINS OMITTED FOR CLARITY or 250 kHz (AD7891-2). The track/hold amplifier acquires an input signal in 600 ns Figure 7. AD7891 to 8X51 Interface (AD7891-1) or 400 ns (AD7891-2). The operation of the track/ The 8X51 provides the LSB of its SBUF register as the first bit hold is essentially transparent to the user. The track/hold amplifier in the serial data stream. The AD7891 expects the MSB of the goes from its tracking mode to its hold mode on the rising edge 6-bit write first. Therefore, the data in the SBUF register must of CONVST. The aperture time for the track/hold (i.e., the be arranged correctly so that this is taken into account. When delay between the external CONVST signal and the track/hold data is to be transmitted to the part, P3.3 is taken low. The actually going into hold) is typically 15 ns. At the end of conversion, 8X51 transmits its data in 8-bit bytes with only eight falling the part returns to its tracking mode. The track/hold starts acquiring clock edges occurring in the transmit cycle. One 8-bit transfer the next signal at this point. is needed to write data to the control register of the AD7891. STANDBY Operation After the data has been transferred, the P3.3 line is taken high The AD7891 can be put into power save or standby mode by to complete the transmission. using the STANDBY pin or the SWSTBY bit of the control When reading data from the AD7891, P3.4 of the 8X51 is taken register. Normal operation of the AD7891 takes place when the low. Two 8-bit serial reads are performed by the 8X51, and STANDBY input is at a Logic 1 and the SWSTBY bit is at a P3.4 is taken high to complete the transfer. Again, the 8X51 Logic 0. When the STANDBY pin is brought low or a 1 is writ- expects the LSB first, while the AD7891 transmits MSB first, so ten to the SWSTBY bit, the part goes into its standby mode of this must be taken into account in the 8X51 software. operation, reducing its power consumption to typically 75 mW. No provision has been made in the given interface to determine The AD7891 is returned to normal operation when the when a conversion has ended. If the conversions are initiated by STANDBY input is at a Logic 1 and the SWSTBY bit is a software, the 8X51 can wait a predetermined amount of time Logic 0. The wake-up time of the AD7891 is normally determined before reading back valid data. Alternately, the falling edge of by the amount of time required to charge the 0.1 mF capacitor the EOC signal can be used to initiate an interrupt service between the REF OUT/REF IN pin and REF GND. If the routine that reads the conversion result from part to part. internal reference is being used as the reference source, this capacitor is charged via a nominal 2 kW resistor. Assuming 10 AD7891 to 68HC11 Serial Interface time constants to charge the capacitor to 12-bit accuracy, this Figure 8 shows a serial interface between the AD7891 and the implies a wake-up time of 2 ms. 68HC11 microcontroller. SCK of the 68HC11 drives SCLK of the AD7891, the MOSI output drives DATA IN of the If an external reference is used, this must be taken into account AD7891, and the MISO input receives data from DATA OUT when working out how long it will take to charge the capacitor. of the AD7891. Ports PC6 and PC7 of the 68HC11 drive the If the external reference has remained at 2.5 V during the time TFS and RFS lines of the AD7891, respectively. the AD7891 was in standby mode, the capacitor will already be charged when the part is taken out of standby mode. Therefore, For correct operation of this interface, the 68HC11 should be the wake-up time is now the time required for the internal configured such that its CPOL bit is a 1 and its CPHA bit is a 0. circuitry of the AD7891 to settle to 12-bit accuracy. This typi- When data is to be transferred to the AD7891, PC7 is taken cally takes 5 ms. If the external reference was also put into low. When data is to be received from the AD7891, PC6 is standby then the wake-up time of the reference, combined with taken low. The 68HC11 transmits and receives its serial data in the amount of time taken to recharge the reference capacitor 8-bit bytes, MSB first. The AD7891 also transmits and receives from the external reference, determines how much time must data MSB first. Eight falling clock edges occur in a read or write elapse before conversions can begin again. cycle from the 68HC11. A single 8-bit write with PC7 low is required to write to the control register. When data has been MICROPROCESSOR INTERFACING written, PC7 is taken high. When reading from the AD7891, AD7891 to 8X51 Serial Interface PC6 is left low after the first eight bits have been read. A second A serial interface between the AD7891 and the 8X51 byte of data is then transmitted serially from the AD7891. When microcontroller is shown in Figure 7. TXD of the 8X51 drives this transfer is complete, the PC6 line is taken high. SCLK of the AD7891, while RXD transmits data to and receives data from the part. The serial clock speed of the 8X51 is slow compared to the maximum serial clock speed of the AD7891, so maximum throughput of the AD7891 is not achieved with this interface. REV. D –14– AD7891 As in the 8X51 circuit in Figure 7, the way the 68HC11 is AD7891 to DSP5600x Serial Interface informed that a conversion is completed is not shown in the Figure 10 shows a serial interface between the AD7891 and the diagram. The EOC line can be used to inform the 68HC11 DSP5600x series of DSPs. When reading from the AD7891, the that a conversion is complete by using it as an interrupt signal. DSP5600x should be set up for 16-bit data transfers, MSB first, The interrupt service routine reads in the result of the conver- normal mode synchronous operation, internally generated word sion. If a software conversion start is used, the 68HC11 can frame sync, and gated clock. When writing to the AD7891, 8-bit wait for 2.0 ms (AD7891-2) or 2.2 ms (AD7891-1) before read- or 16-bit data transfers can be used. The frame sync signal from ing from the AD7891. the DSP5600x must be inverted before being applied to the RFS and TFS inputs of the AD7891, as shown in Figure 10. To monitor the conversion time of the AD7891, a scheme such PC7 RFS as those outlined in previous interfaces with EOC can be used. PC6 TFS This can be implemented by connecting the EOC line directly 68HC11* AD7891* to the IRQA input of the DSP5600x. SCK SCLK MOSI DATA IN DSP5600x* MOSO DATA OUT RFS FST (SC2) TFS *ADDITIONAL PINS OMITTED FOR CLARITY AD7891* SCK SCLK Figure 8. AD7891 to 68HC11 Interface STD DATA IN AD7891 to ADSP-21xx Serial Interface SRD DATA OUT An interface between the AD7891 and the ADSP-21xx is shown in Figure 9. In the interface shown, either SPORT0 or SPORT1 *ADDITIONAL PINS OMITTED FOR CLARITY can be used to transfer data to the AD7891. When reading from the part, the SPORT must be set up with a serial word Figure 10. AD7891 to DSP5600x Serial Interface length of 16 bits. When writing to the AD7891, a serial word AD7891 to TMS320xxx Serial Interface length of 6 bits or more can be used. Other setups for the The AD7891 can be interfaced to the serial port of TMS320xxx serial interface on the ADSP-21xx internal SCLK use alternate DSPs, as shown in Figure 11. External timing generation circuitry framing mode and active low framing signal. Normally, the is necessary to generate the serial clock and syncs necessary for EOC line from the AD7891 would be connected to the IRQ2 the interface. line of the ADSP-21xx to interrupt the DSP at the end of a conversion (not shown in diagram). TIMING GENERATION CIRCUITRY RFS RFS TMS320xxx* RFS FSR TFS TFS ADSP-21xx* AD7891* FSX TFS SCLK SCLK AD7891* CLKR DT DATA IN SCLK CLKX DR DATA OUT DX DATA IN *ADDITIONAL PINS OMITTED FOR CLARITY DR DATA OUT Figure 9. AD7891 to ADSP-21xx Serial Interface *ADDITIONAL PINS OMITTED FOR CLARITY Figure 11. AD7891 to TMS320xxx Serial Interface REV. D –15– AD7891 PARALLEL INTERFACING The parallel interface on the AD7891 is fast enough to interface The parallel port on the AD7891 allows the device to be interfaced to the TMS32020 with no extra wait states. If high speed glue to microprocessors or DSP processors as a memory mapped logic, such as 74AS devices, are used to drive the WR and RD or I/O mapped device. The CS and RD inputs are common to lines when interfacing to the TMS320C25, then again no wait all memory peripheral interfacing. Typical interfaces to different states are necessary. However, if slower logic is used, data accesses processors are shown in Figures 12 to 15. In all the interfaces may be slowed sufficiently when reading from and writing to the shown, an external timer controls the CONVST input of the part to require the insertion of one wait state. In such a case, AD7891 and the EOC output interrupts the host DSP. this wait state can be generated using the single OR gate to combine the CS and MSC signals to drive the READY line of AD7891 to ADSP-21xx the TMS320C25, as shown in Figure 13. Extra wait states are Figure 12 shows the AD7891 interfaced to the ADSP-21xx necessary when using the TMS320C5x at their fastest clock series of DSPs as a memory mapped device. A single wait state speeds. Wait states can be programmed via the IOWSR and may be necessary to interface the AD7891 to the ADSP-21xx CWSR registers (see the TMS320C5x User Guide for details). depending on the clock speed of the DSP. This wait state can be programmed via the data memory wait state control register Data is read from the ADC using the following instruction: of the ADSP-21xx (please see the ADSP-2100 family Users IN D, ADC Manual for details). The following instruction reads data where D is the memory location where the data is to be stored, from the AD7891. and ADC is the I/O address of the AD7891. MR = DM (ADC) AD7891 to TMS320C3x where ADC is the address of the AD7891. Figure 14 shows a parallel interface between the AD7891 and the TMS320C3x family of DSPs. The AD7891 is interfaced to the expansion bus of the TMS320C3x. A single wait state is A13 TO A0 ADDRESS BUS required in this interface. This can be programmed using the ADDR WTCNT bits of the expansion bus control register (see the ADSP-21xx* DECODE TMS320C3x Users Guide for details). Data from the AD7891 CS DMS EN can be read using the following instruction: WR WR AD7891* LDI ¥ ARn, Rx RD RD IRQ2 EOC where ARn is an auxiliary register containing the lower 16 bits of the address of the AD7891 in the TMS320C3x memory D23 TO D8 DATA BUS DB11 TO DB0 space, and Rx is the register into which the ADC data is loaded. *ADDITIONAL PINS OMITTED FOR CLARITY XA15 TO XA0 ADDRESS BUS Figure 12. AD7891 to ADSP-21xx Parallel Interface AD7891 to TMS32020, TMS320C25, and TMS320C5x ADDR TMS320C3x* CS DECODE Parallel interfaces between the AD7891 and the TMS32020, AD7891* TMS320C25, and TMS320C5x family of DSPs are shown in IOSTRB WR Figure 13. The memory mapped address chosen for the XR/W AD7891 should be chosen to fall in the I/O memory space of RD the DSPs. INTx EOC XD23 TO XD0 EXPANSION DATA BUS DB11 TO DB0 ADDRESS BUS A15 TO A0 TMS32020/ *ADDITIONAL PINS OMITTED FOR CLARITY ADDR TMS320C25/ CS IS EN DECODE TMS320C5x* Figure 14. AD7891 to TMS320C3x Parallel Interface READY TMS320C25 AD7891* ONLY MSC STRB WR R/W RD INTx EOC DATA BUS D23 TO D0 DB11 TO DB0 *ADDITIONAL PINS OMITTED FOR CLARITY Figure 13. AD7891 to TMS32020/TMS320C25/TMS320C5x Parallel Interface REV. D –16– AD7891 AD7891 to DSP5600x Digital lines running under the device should be avoided because Figure 15 shows a parallel interface between the AD7891 and these couple noise onto the die. The analog ground plane should the DSP5600x series of DSPs. The AD7891 should be mapped be allowed to run under the AD7891 to avoid noise coupling. into the top 64 locations of Y data memory. If extra wait states The power supply lines of the AD7891 should use as large a are needed in this interface, they can be programmed using the trace as possible to provide low impedance paths and reduce the Port A Bus control register (see the DSP5600x Users Manual effects of glitches on the power supply line. Fast switching sig- for details). Data can be read from the AD7891 using the fol- nals like clocks should be shielded with digital ground to avoid lowing instruction: radiating noise to other parts of the board and should never be run near the analog inputs. Avoid crossover of digital and analog MOVEO Y: ADC, X0 signals. Traces on opposite sides of the board should run at right where ADC is the address in the DSP5600x address space to angles to each other. This reduces the effects of feedthrough which the AD7891 has been mapped. through the board. A microstrip technique is by far the best technique but is not always possible with a double-sided board. In this technique, the component side of the board is dedicated A15 TO A0 ADDRESS BUS to ground plane while signal traces are placed on the solder side. DSP56000/ DSP56002* X/Y ADDR The AD7891 should have ample supply bypassing located as close CS DECODE DS to the package as possible, ideally right up against the device. WR WR One of the V pins (Pin 10 of the PLCC package and Pin 4 DD AD7891* RD RD on the MQFP package) mainly drives the analog circuitry on the chip. This pin should be decoupled to the analog ground IRQ EOC plane with a 10 mF tantalum bead capacitor in parallel with a D23 TO D0 DATA BUS DB11 TO DB0 0.1 mF capacitor. The other V pin (Pin 19 on the PLCC DD package and Pin 13 on the MQFP package) mainly drives *ADDITIONAL PINS OMITTED FOR CLARITY digital circuitry on the chip. This pin should be decoupled to the digital ground plane with a 0.1 mF capacitor. The 0.1 mF Figure 15. AD7891 to DSP5600x Parallel Interface capacitors should have low effective series resistance (ESR) and Power Supply Bypassing and Grounding effective series inductance (ESI), such as the common ceramic In any circuit where accuracy is important, careful consideration types or surface mount types, which provide a low impedance of the power supply and ground return layout helps to ensure path to ground at high frequencies to handle transient currents the specified performance. The PCB on which the AD7891 is due to internal logic switching. Figure 16 shows the mounted should be designed such that the analog and digital recommended decoupling scheme. sections are separated and confined to certain areas of the board. This facilitates the use of ground planes that can be separated easily. A minimum etch technique is generally best for ground AD7891 planes because it gives the best shielding. Digital and analog V (PIN 10, PLCC DD PIN 4, MQFP) 0.1�F ground planes should be joined at only one place. If the AD7891 10�F AGND is the only device requiring an AGND to DGND connection, AGND then the ground planes should be connected at the AGND and DGND pins of the AD7891. If the AD7891 is in a system where V (PIN 19, PLCC DD multiple devices require an AGND to DGND connection, the PIN 13, MQFP) 0.1�F connection should still be made at one point only, a star ground DGND point established as close as possible to the AD7891. Figure 16. Recommended Decoupling Scheme for the AD7891 REV. D –17– AD7891 AD7891 PERFORMANCE Dynamic Performance Linearity The AD7891 contains an on-chip track/hold amplifier, allowing The linearity of the AD7891 is primarily determined by the the part to sample input signals of up to 250 kHz on any of its on-chip 12-bit DAC. This is a segmented DAC that is laser input channels. Many of the AD7891’s applications require it to trimmed for 12-bit integral linearity and differential linearity. sequence through low frequency input signals across its eight Typical INL for the AD7891 is ±0.25 LSB while typical DNL channels. There may be some applications, however, for which is ±0.5 LSB. the dynamic performance of the converter on signals of up to 250 kHz input frequency is of interest. It is recommended for Noise these wider bandwidth signals that the hardware conversion In an ADC, noise exhibits itself as code uncertainty in dc appli- start method of sampling is used. cations and as the noise floor (in an FFT for example) in ac applications. In a sampling ADC, such as the AD7891, all These applications require information on the spectral content information about the analog input appears in the baseband from of the input signal. Signal-to-(noise + distortion), total dc to half the sampling frequency. The input bandwidth of the harmonic distortion, peak harmonic or spurious tone, and track/hold amplifier exceeds the Nyquist bandwidth and, intermodulation distortion are all specified. Figure 18 shows a therefore, an antialiasing filter should be used to remove typical FFT plot of a 10 kHz, ±10 V input after being digitized unwanted signals above f /2 in the input signal in applications by the AD7891-1 operating at 500 kHz, with the input connected S where such signals exist. for ±10 V operation. The signal-to-(noise + distortion) ratio is 72.2 dB and the total harmonic distortion is –87 dB. Figure 19 Figure 17 shows a histogram plot for 16384 conversions of a dc shows a typical FFT plot of a 100 kHz, 0 V to 5 V input after input signal using the AD7891-1. The analog input was set at being digitized by the AD7891-2 operating at 500 kHz, with the the center of a code transition in the following way. An initial dc input connected for 0 V to 5 V operation. The signal-to-(noise + input level was selected and a number of conversions were distortion) ratio is 71.17 dB and the total harmonic distortion made. The resulting histogram was noted and the applied level is –82.3 dB. It should be noted that reading from the part was adjusted so that only two codes were generated with an during conversion does have a significant impact on dynamic equal number of occurrences. This indicated that the transition performance. Therefore, for sampling applications, it is point between the two codes had been found. The voltage level recommended not to read during conversion. at which this occurred was recorded. The other edge of one of these two codes was then found in a similar manner. The dc 2048 POINT FFT 0 level for the center of code could then be calculated as the average of the two transition levels. The AD7891-1 inputs were configured for the ±5 V input range and the data was read –30 from the part in parallel mode after conversion. Similar results SNR = 72.2dB have been found with the AD7891-1 on the ±10 V range and on –60 all input ranges of the AD7891-2. The same performance is achieved in serial mode, again with the data read from the AD7891-1 after conversion. All the codes, except for 3, appear –90 in one output bin, indicating excellent noise performance from the ADC. –120 18000 16381 CODES –150 16000 F /2 S 14000 Figure 18. Typical AD7891-1 FFT Plot 12000 2048 POINT FFT 0 10000 8000 –30 6000 SNR = 71.17dB 4000 –60 2000 1 CODE 2 CODES 0 2148 2149 2150 –90 OUTPUT CODE Figure 17. Typical Histogram Plot (AD7891-1) –120 –150 F /2 S Figure 19. Typical AD7891-2 FFT Plot REV. D –18– NUMBER OF OCCURRENCES dB dB AD7891 Effective Number of Bits 12.0 The formula for signal-to-(noise + distortion) ratio (see Terminology 11.9 section) is related to the resolution or number of bits of the 11.8 converter. Rewriting the formula gives a measure of performance 11.7 expressed in effective number of bits (ENOB). 11.6 ENOB=- SNR 17./ 6 60. 2 AD7891-2 ENOB () 11.5 where SNR is the signal-to-(noise + distortion) ratio. 11.4 The effective number of bits for a device can be calculated from 11.3 its measured SNR. Figure 20 shows a typical plot of effective 11.2 number of bits versus frequency for the AD7891-1 and the AD7891-1 ENOB 11.1 AD7891-2 from dc to 200 kHz. The sampling frequency is 500 kHz. The AD7891-1 inputs were configured for ±10 V 11.0 06 20 400 80 100 120 140 160 180 200 operation. The AD7891-2 inputs were configured for 0 to 5 V FREQUENCY – kHz operation. The AD7891-1 plot only goes to 100 kHz as a Figure 20. Effective Number of Bits vs. Frequency ±10 V sine wave of sufficient quality was unavailable at higher frequencies. Figure 20 shows that the AD7891-1 converts an input sine wave of 100 kHz to an effective number of bits of 11 which equates to a signal-to-(noise + distortion) level of 68.02 dBs. The AD7891-2 converts an input sine wave of 200 kHz to an effective number of bits of 11.07, which equates to a signal-to-(noise + distortion) level of 68.4 dBs. OUTLINE DIMENSIONS 44-Lead Plastic Leaded Chip Carrier [PLCC] (P-44A) Dimensions shown in inches and (millimeters) 0.180 (4.57) 0.048 (1.22) 0.165 (4.19) 0.042 (1.07) 0.056 (1.42) 0.020 (0.51) 0.042 (1.07) MIN 6 40 0.048 (1.22) 7 39 PIN 1 0.021 (0.53) IDENTIFIER 0.042 (1.07) 0.013 (0.33) 0.630 (16.00) BOTTOM VIEW 0.050 TOP VIEW 0.590 (14.99) (PINS UP) (PINS DOWN) (1.27) BSC 0.032 (0.81) 0.026 (0.66) 17 29 18 28 0.040 (1.01) R 0.656 (16.66) 0.025 (0.64) 0.120 (3.05) SQ 0.650 (16.51) 0.090 (2.29) 0.695 (17.65) SQ 0.685 (17.40) COMPLIANT TO JEDEC STANDARDS MO-047AC CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN REV. D –19– EFFECTIVE NUMBER OF BITS AD7891 OUTLINE DIMENSIONS 44-Lead Metric Quad Flat Package [MQFP] (S-44-2) Dimensions shown in millimeters 1.03 13.90 BSC SQ 0.88 2.45 MAX 0.73 33 23 34 22 SEATING PLANE 10.00 TOP VIEW BSC SQ (PINS DOWN) 7� VIEW A 2.10 0� PIN 1 2.00 44 12 1.95 0.25 MIN 1 11 COPLANARITY 0.10 0.45 0.80 VIEW A 0.30 BSC ROTATED 90� CCW COMPLIANT TO JEDEC STANDARDS MO-112-AA-1 Revision History Location Page 4/04—Data Sheet changed from REV. C to REV. D. Changes to SPECIFICATIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 Changes to PIN FUNCTION DESCRIPTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 Changes to PARALLEL INTERFACE MODE FUNCTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 Changes to SERIAL INTERFACE MODE FUNCTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 Changes to CONTROL REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 Changes to AD7891 to 8X51 Serial Interface section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 Changes to Figure 10 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 Changes to Figure 11 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 Changes to Power Supply Bypassing and Grounding . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 Changes to Figure 16 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 01/02—Data Sheet changed from REV. B to REV. C. Changed page 7 to page 6 and moved page 6 to page 9 to keep Pin Configurations together with Pin Function descriptions. Edits to CONTROL REGISTER . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 Text added to CONVERTER DETAILS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 Edits to Figure 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 02/01—Data Sheet changed from REV. A to REV. B. PQFP designation changed to MQFP throughout. Edit to FEATURES, Single Supply Low Power Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to mW (90 to 82) in last paragraph of left hand column . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Edits to POWER REQUIREMENTS section of Specifications table . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 REV. D –20– C01358–0–4/04(D)